CA1198169A - Digital radio systems - Google Patents
Digital radio systemsInfo
- Publication number
- CA1198169A CA1198169A CA000403823A CA403823A CA1198169A CA 1198169 A CA1198169 A CA 1198169A CA 000403823 A CA000403823 A CA 000403823A CA 403823 A CA403823 A CA 403823A CA 1198169 A CA1198169 A CA 1198169A
- Authority
- CA
- Canada
- Prior art keywords
- frequency
- signal
- radio
- digital
- stage
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired
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Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B7/00—Radio transmission systems, i.e. using radiation field
- H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
- H04B7/12—Frequency diversity
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L1/00—Arrangements for detecting or preventing errors in the information received
- H04L1/02—Arrangements for detecting or preventing errors in the information received by diversity reception
- H04L1/04—Arrangements for detecting or preventing errors in the information received by diversity reception using frequency diversity
Abstract
ABSTRACT OF THE INVENTION
DIGITAL RADIO SYSTEMS
For tropospheric-scatter and short-wave transmission links for digital data signals employing frequency modulation, frequency diversity is employed to counter any selective fading resulting from multi-path propagation, the digital signal being supported by redundancy using a compound frequency changer stage comprising at least three radio frequencies, the digital signal, together with at least one additional oscillation, in fact an additional fundamental oscillation which determines the frequency spacing in the compound frequency mixer stage, is fed to the input of a frequency modulator (M). At the receiving end, the radio-frequency carriers from the frequency mixer stage each modulated with the useful signal, are all converted by coherent mixing into the same frequency level and fed to a combiner (K) to obtain a sum signal which has an optimum signal-to-noise ratio.
DIGITAL RADIO SYSTEMS
For tropospheric-scatter and short-wave transmission links for digital data signals employing frequency modulation, frequency diversity is employed to counter any selective fading resulting from multi-path propagation, the digital signal being supported by redundancy using a compound frequency changer stage comprising at least three radio frequencies, the digital signal, together with at least one additional oscillation, in fact an additional fundamental oscillation which determines the frequency spacing in the compound frequency mixer stage, is fed to the input of a frequency modulator (M). At the receiving end, the radio-frequency carriers from the frequency mixer stage each modulated with the useful signal, are all converted by coherent mixing into the same frequency level and fed to a combiner (K) to obtain a sum signal which has an optimum signal-to-noise ratio.
Description
~ 2~-~
The inVention ~el~tes to digital radio syste-m-s suitable fox tropospheric~scatter and other short-wave links, wherein, at the trans~itting end, a digital data signal i5 impressed onto a radio~requency carrier by fre~uency modulation, and is reconstituted at the receiving end by suitable demodulation of the recei~ed carrier to be available for further processing.
Selective ~ading~ particu~arly that caused by multiple path propagation in the case of tropospheric-scatter and short-wave linksr restricts the use of these links for the transmission of digital data communications. As indicated for .
~mple in the German Paten~ specification 26 28 997, in the tr~n~m;~sion of digital frequency - modulated data flows~ under certain circumstances multiple.path wave propagations may lead to s~rious reception disturbancest especially when polydixect-ional antennae are used. Reflections from different directions mean that wave fronts emitted from the transmitti~g antennae are in~ident upon the receiving antennae after different transit i times. As a result of the vectorial addition of these wave fronts, the antennae base voltage experiences an amplitude response and phase response which is dependent both upon frequency and upon location. Because of the distortions and energy reduction~ (~;n;m~) which this energy distribution produces, for many frequencies and locations it causes a loss ?5 of legibility of digital received signals, When the locating points of transmitter and xeceiver are pre~determined, the frequency dependent energy distribution results in a succession -3~
of relativel~ nar~ow energy ~1 n1~ and relatively wide eneryy maxima. The ~reguency spacing between two consecutive maxLma or m;n;~ is referred to as the coherency band width o th~ radio link, In order to safeguard the useful signal transmission it is known~ ~or example from the German Patent specification AS 25 58 557, to use so-called diversity measures. This entails an exploitation of the act that with diferent radio frequencies (frequency diversity~ the described drop in level does not occur simultaneously and therefore parallel transmission at two or more frequencies increases the resistance to break downs. In addition to frequency diversity there also exists so-called space diversity, wherein receiving antennae are mutually spaced at an adequate distance from one another so that. as a result of different transit ~ime conditions~ the advexse results o~ these multiple path effects can be reduced to a considerably lower degree of probability. However, the need to provide redundanc~ by the use of plural ~hannels/ means that diversity methods involve expenditures that are substantially increased.
One object of the present invention is, to provide ~ radio system o~ the type described in the introduction, which is equipped with frequency diversity in a manner such as to provide the requisite redundancy with low technical outlay in circuitry and operating costs.
The invention consists in a digital radio system of the type llsed in tropospheric-scatter and short~wave transmission links, in which means are proYided at the transmitting end to impress the useful digital signal upon 6~3 a ~adio ~ ~requenc~ carxie~ by ~equency ~odulation and means provided at the receiVing end for demodulation of the received carrier a.nd the provision Qf a reconstituted data signal for further processing, frequency diversity being employed in order to counter transmission disturbances of the type caused by seIected fading resulting from multi-path propagation, the digital signal to be transmitted being fed at the transmltting end to a compound ~requency changer stage comprising at least two local oscillation frequency sourcesr one a fundamental oscillation which determines the frequency of the frequency spacing in the compound frequency changer stage~ all being fed to the input of a frequency modulator, and at the receiving end the radio-frequency carrier, modulated ~ith the useful sigllal, being converted back to an equal frequency position in converters by means of mutually coherent local oscillat.ions from a conversion oscillator arrangement, and subsequently fed to a combiner to form a sum signal which exhibits an optimum signal-to-noise ratio.
Thus, the invention is based on the flln~m~ntal recognition that the support of the useful digital signal, which is to be transmitted, by means of a radio frequency allocation can be achieved in an extremely simple manner in the frequency modulator~ using an additional undamental oscillation whose frequency determines the allocation spacingO
Here the radio-frequency sum signal possesses an envelope curve which contains no amplitude modulation components. This sign~l can be a~pli~ied to the ~equired txanSmitting power in an extremel~ s~ple ~annerr for exampl~ usiny non-linear Class C a~plifiers without gi~ing rise to distortion. No string~nt requirements are imposed upon the receiving end intermediate S frequency a~plifier relating to linearity following the selection of an allocation sub~signal as each of the sub-sign~ls represents a pure FM-signal.
Particularly favourable conditions are achieved if the carrier frequencies of the operating fre~uency-modulat~d signals have a frequency allocation scheme determined taking into account the Bessel functions and a phase determined for at least approximately e~ual amplitude, and for this purpose the additional f~ Amental oscillation and possibly further additional harmonics can be adjusted in amplitude, and the additional harmonics c~n also be adjusted in phase. Here at least one additional harmonic can be provided to compensate undesired secondaries of the radio-fre~uency frequency all-ocation scheme.
!` For optimum effectiveness the width of the radio~
~0 frequency transmitting spectrum should equal approximately half that of the occurrIng coherency bandwidths/ as this ensures that on the occurrence of a selecti~e break in level occurring as a result of multi-path propagation, only one of the useful modulated carriers of the frequency scheme is affected, wllere the remaining, modulatedr carriers remain largely undisturbed. This occurs because, as already refexred to in the introduction, the energy distribution over the frequenc~ in the case o~ ~ulti~path prop~gation exhibits relatively narrow - band level~m; nl~,~ but relatively wide level maxima.
The invention will now be described with reference to the drawingst in which:-Figure 1 is a block schematic circuit diagram of the relevant parts o~ a transmitting station in one exemplary embodiment of a radio system constructed in accordance with the in~ention;
Figure 2 is ~ blosk schematic circuit diagram of the related parts at the receiving end of this embodiment o a radio system in accordance with the in~ention;
Figures 3 and 4 are graphs showing frequency diagrams which explain in detai.l the function of the trans-mitting end circuit diagram shown in Figure 1; and Figure S is a further explanatory graph which indicates the probability function of the receiving level in dependence upon the availàbility of a radio-frequency ( channel in ~.
A transmitting station S, partly illustrated in the block schematic.circuit diagram shown in Figure 1, comprises a data source DQ, whose output is connected to an input of an adder stage AS via a low-pass filter TP. The other inputs of the a~der stage AS receive from a local oscillation generator arrangement GA an additional flln~menta oscillation with the fre~uency fzO and additional harmonies ~f the frequencies fzl to fzn, The suppl~ lines of the ~dditional ~undamental o~cillation and the additiQnal harmonics contain xespecti~e ~dju~table attenuation elements, aO, al to an, whilst the supply lines ~or the additional harmonics also contain respective adjustable phase shifting elements, bl to bn. The sum signal, co~posed of the useful digital signal supplied from the data source DQ, the additional flln~mPntal oscillation and the additional ha~monics, is fed to the input of a ~requency modulator M/ which consists of a high frequency local oscillator with means by which it can be modulated in freque~cy. The modulator output is fed to a transmitter output stage SE, wh.ich preferably consists of a Class C amplifier D The transmitter output stage SE eeds on antenna Ao The attenuating elements a~, al to an serve to adjust the frequency range, which is dependent upon the additional fundamental oscillation and the additional harmonics.
The adjustable phase shifting elements bl to bn additionally serve to adjust the relative phases of the additional harmonics. The fr~quency fzO of the additional fundamental oscillation detenmines the spacing o the components in the modulator-output radio-frequency plan. Taking into account the Bessel functions which describe the frequency modulation and the phases thereof, the modulator-output frequency plan can be adjusted to be such that all the xaster lines with a mutual spacing of the frequency fz~ possess the same amplitude.
Furthermore one or t~o of the highest value additional harmonics can be used, by appxopriate adjustment o~ their attenuating elements and phase shift elements, to at least approximately compensate undesi~ed subsidiaxy spectxal lines of the desired frequency p~ttern.
The ~requency-modulated ~requency spectrum which is emitted at the trans~itting end, and in which each radio-frequency carrier is modulated in frequency with theuseful digital informatiQn, contains no amplitude modulation components in its envelope curvet so that non-linear amplifiers can be used at the transmitting and receiving end without any fear of distortion.
The frequency-modulated sum signal received at the antenna A of the receiver E shown in part in Figure 2 is amplified in a receiving amplifier E~, is subsequently converted into a low frequency position in a first receiving mixer stage EUl with the aid of a local oscillation supplied from a local oscillator Ulr and is fed to a selective amplifier SV. The output of the. selective ampli~ier SV feeds the received, converted, frequency-modulate~ signal to be distributed between a number of channels which correspond to . the numbPr of raster fxequencies within the requency field, 20 and in each channel the relevant frequency-modulated carrier is converted to a common intermediate frequency~ For this purpose each of these channels, Kol K l+ to ~n~ and Kl to Kn consists of an input-end intermediate mixer stage U~ which is followed b~ a b~nd pass ~ilter BP and an amplifier V.
For this conversion mutually coherent local oscillations which possess the frequencies ~O~ fl~ to fn-~ a 1- n~
supplied by a common local oscillator arrangement OA. The mutual frequency spacing of the conversion oscillations is equal to the fxequenc~ ~zO o~ the transmitting end additional flln~m~ntal oscillation. ~t their outputs the channels ~O, Kl+ to KntJ ana Kl to Kn are united in a combiner K in such manner that the output su~ signal exhibits an optimum signal-S to-noise ratio. The sum signal for~ed in this way, which is prese~t at the output of the combiner K, is converted into the base band position in a second mixer stage EU2 comprising a local oscillator 02, is subsequently demodulated in a demodulator DN, and the original useful digital signal thus obtained is fed to a data sink DS.
Figure 3 illustrates the spectral diagram at the output of the frequency modulator M illustrated in Figure 1 for an additional fllnd~mental oscillation of the frequency 3 M~z, without any useful signal, and without additional harmonics.
15~ As can be seen from this diagram, a requency pattern is composed of spectral lines mutually spaced by 3 MHz. By suitable adjustment of the frequency ranger for three spectxal lines an identical amplitude is achieved which is followed, i on both sides, by a secondary line attenuated by approximately 25dB. By appropriate adjustment o the frequency range it would also be possiblel apart from the attenuated secondary lines, to produce a frequency pattern comprising two spectral lines spaced by 6 ~z~
The ~requency pattern composed o~ these thxee radio frequencies-of identical amplitude as useful carriers~
and which p~ssesses a total width of 6 MHæ, corresponds for example to approximately half the coherency bandwidths of a - ~. o troposphexic~scatte~ connection. Thus an~ selectlve breaks in level will only suppre~s one of.the radio frequency carriersS whilst the other two remain largely undisturbed.
The signal spectrum illustrated in Figure 4 corresponds to that shown in Figure 3, with the difference that the actual useul signal is likewise fed to the frequency modulator via the adder stage AS in Figure 1. As can be seen from Figure ~, each of the radio-frequency carriers sp~ced by 3 MHz is itself modulated in frequency by the useful signal in the same ~nner.
As has been represented in association with Figures 1 and 2, with the aid of additional harmonics it is possible to increase the number of radio frequency carriers provided in the frequency pattern to 5, 7 or 9, etc. In addition it is possible, with the aid of additional harmonics, to at least approximately suppress undesired secondary lines of the spectrum, such as the frequency spectrum shown in Figure 3 and 4 possesses.
The distxibution of the useful digital signal by means of the special FM-modulation in a system constructed in accordance with the invention, between for example three equally spaced radio frequency carriers, as shown in Figure 3 and 4, results in a po~er reduction of each carrier of appr~ximately 4.8 dB in comparison to the use of one ~ingle caxrier. Taking into account the low energy content of a spectral line (4.8 dB in the case of three radio-frequency carriers) r Figure 5 represents probability curves for the ~ 3;c3 likely ~um ~ useful l~yel. The diagram in ~ ure 5 contains two groups af cuX~eS~ e~ch o~ which lllustrate the likely signal level in dependence upon the channel availability within the limits of 0.1 to 99~. The dash~dotted group of curves WK indicates comparison cur~es of a conventional radio system operating with and without frequency diversityl whereas the solid - line curves referenced 1, 2 and 3 illustrate the results achieved by a system constructed in accordance with the invention.
The probability curve WK, with the FDM
diversity degree D = 1, indicates the course of the Raleigh channel. The corresponding proba~ility curves WK for a diversity degree D = 2 and for a diversity degree D ~ 4 illustrate the corresponding improvement in the recæption conditions when two-fold or four-fold frequency diversity is employed~ Curves 1, 2 and 3 differ from one another only in respect of the spread band widths which is used. In the case of curve 1 the spread band widths amounts to 19 MHz, in the case of curves 2 it amounts to 1~ MHz and in the case of curve 3 it amounts to 6 MHz. As can be seen from the diagram in Figure 5, in the present exampl~, with a frequency pattern comprising three carriers, with 99.9% availability of the system, equivalent FDM diversity degrees of D = 2 to D = 3 can be achieved. The reduction in the fading characteristics in comparison to the Raleigh channel here amounts to 15 to 20 dB, so that in the exemplary embodiment a residual fading of anly 3 to 8 dB is likely. ~hen frequency arxangements comprisin~ ~ore than three radio frequencies are used, the frequency bandwidths of which can also exceed half of one coherency bandwidth,,o~ the s~stem, a further improvement can be achieved ln the reduction of the fading characteristics in comparison to the Raleigh channel.
The inVention ~el~tes to digital radio syste-m-s suitable fox tropospheric~scatter and other short-wave links, wherein, at the trans~itting end, a digital data signal i5 impressed onto a radio~requency carrier by fre~uency modulation, and is reconstituted at the receiving end by suitable demodulation of the recei~ed carrier to be available for further processing.
Selective ~ading~ particu~arly that caused by multiple path propagation in the case of tropospheric-scatter and short-wave linksr restricts the use of these links for the transmission of digital data communications. As indicated for .
~mple in the German Paten~ specification 26 28 997, in the tr~n~m;~sion of digital frequency - modulated data flows~ under certain circumstances multiple.path wave propagations may lead to s~rious reception disturbancest especially when polydixect-ional antennae are used. Reflections from different directions mean that wave fronts emitted from the transmitti~g antennae are in~ident upon the receiving antennae after different transit i times. As a result of the vectorial addition of these wave fronts, the antennae base voltage experiences an amplitude response and phase response which is dependent both upon frequency and upon location. Because of the distortions and energy reduction~ (~;n;m~) which this energy distribution produces, for many frequencies and locations it causes a loss ?5 of legibility of digital received signals, When the locating points of transmitter and xeceiver are pre~determined, the frequency dependent energy distribution results in a succession -3~
of relativel~ nar~ow energy ~1 n1~ and relatively wide eneryy maxima. The ~reguency spacing between two consecutive maxLma or m;n;~ is referred to as the coherency band width o th~ radio link, In order to safeguard the useful signal transmission it is known~ ~or example from the German Patent specification AS 25 58 557, to use so-called diversity measures. This entails an exploitation of the act that with diferent radio frequencies (frequency diversity~ the described drop in level does not occur simultaneously and therefore parallel transmission at two or more frequencies increases the resistance to break downs. In addition to frequency diversity there also exists so-called space diversity, wherein receiving antennae are mutually spaced at an adequate distance from one another so that. as a result of different transit ~ime conditions~ the advexse results o~ these multiple path effects can be reduced to a considerably lower degree of probability. However, the need to provide redundanc~ by the use of plural ~hannels/ means that diversity methods involve expenditures that are substantially increased.
One object of the present invention is, to provide ~ radio system o~ the type described in the introduction, which is equipped with frequency diversity in a manner such as to provide the requisite redundancy with low technical outlay in circuitry and operating costs.
The invention consists in a digital radio system of the type llsed in tropospheric-scatter and short~wave transmission links, in which means are proYided at the transmitting end to impress the useful digital signal upon 6~3 a ~adio ~ ~requenc~ carxie~ by ~equency ~odulation and means provided at the receiVing end for demodulation of the received carrier a.nd the provision Qf a reconstituted data signal for further processing, frequency diversity being employed in order to counter transmission disturbances of the type caused by seIected fading resulting from multi-path propagation, the digital signal to be transmitted being fed at the transmltting end to a compound ~requency changer stage comprising at least two local oscillation frequency sourcesr one a fundamental oscillation which determines the frequency of the frequency spacing in the compound frequency changer stage~ all being fed to the input of a frequency modulator, and at the receiving end the radio-frequency carrier, modulated ~ith the useful sigllal, being converted back to an equal frequency position in converters by means of mutually coherent local oscillat.ions from a conversion oscillator arrangement, and subsequently fed to a combiner to form a sum signal which exhibits an optimum signal-to-noise ratio.
Thus, the invention is based on the flln~m~ntal recognition that the support of the useful digital signal, which is to be transmitted, by means of a radio frequency allocation can be achieved in an extremely simple manner in the frequency modulator~ using an additional undamental oscillation whose frequency determines the allocation spacingO
Here the radio-frequency sum signal possesses an envelope curve which contains no amplitude modulation components. This sign~l can be a~pli~ied to the ~equired txanSmitting power in an extremel~ s~ple ~annerr for exampl~ usiny non-linear Class C a~plifiers without gi~ing rise to distortion. No string~nt requirements are imposed upon the receiving end intermediate S frequency a~plifier relating to linearity following the selection of an allocation sub~signal as each of the sub-sign~ls represents a pure FM-signal.
Particularly favourable conditions are achieved if the carrier frequencies of the operating fre~uency-modulat~d signals have a frequency allocation scheme determined taking into account the Bessel functions and a phase determined for at least approximately e~ual amplitude, and for this purpose the additional f~ Amental oscillation and possibly further additional harmonics can be adjusted in amplitude, and the additional harmonics c~n also be adjusted in phase. Here at least one additional harmonic can be provided to compensate undesired secondaries of the radio-fre~uency frequency all-ocation scheme.
!` For optimum effectiveness the width of the radio~
~0 frequency transmitting spectrum should equal approximately half that of the occurrIng coherency bandwidths/ as this ensures that on the occurrence of a selecti~e break in level occurring as a result of multi-path propagation, only one of the useful modulated carriers of the frequency scheme is affected, wllere the remaining, modulatedr carriers remain largely undisturbed. This occurs because, as already refexred to in the introduction, the energy distribution over the frequenc~ in the case o~ ~ulti~path prop~gation exhibits relatively narrow - band level~m; nl~,~ but relatively wide level maxima.
The invention will now be described with reference to the drawingst in which:-Figure 1 is a block schematic circuit diagram of the relevant parts o~ a transmitting station in one exemplary embodiment of a radio system constructed in accordance with the in~ention;
Figure 2 is ~ blosk schematic circuit diagram of the related parts at the receiving end of this embodiment o a radio system in accordance with the in~ention;
Figures 3 and 4 are graphs showing frequency diagrams which explain in detai.l the function of the trans-mitting end circuit diagram shown in Figure 1; and Figure S is a further explanatory graph which indicates the probability function of the receiving level in dependence upon the availàbility of a radio-frequency ( channel in ~.
A transmitting station S, partly illustrated in the block schematic.circuit diagram shown in Figure 1, comprises a data source DQ, whose output is connected to an input of an adder stage AS via a low-pass filter TP. The other inputs of the a~der stage AS receive from a local oscillation generator arrangement GA an additional flln~menta oscillation with the fre~uency fzO and additional harmonies ~f the frequencies fzl to fzn, The suppl~ lines of the ~dditional ~undamental o~cillation and the additiQnal harmonics contain xespecti~e ~dju~table attenuation elements, aO, al to an, whilst the supply lines ~or the additional harmonics also contain respective adjustable phase shifting elements, bl to bn. The sum signal, co~posed of the useful digital signal supplied from the data source DQ, the additional flln~mPntal oscillation and the additional ha~monics, is fed to the input of a ~requency modulator M/ which consists of a high frequency local oscillator with means by which it can be modulated in freque~cy. The modulator output is fed to a transmitter output stage SE, wh.ich preferably consists of a Class C amplifier D The transmitter output stage SE eeds on antenna Ao The attenuating elements a~, al to an serve to adjust the frequency range, which is dependent upon the additional fundamental oscillation and the additional harmonics.
The adjustable phase shifting elements bl to bn additionally serve to adjust the relative phases of the additional harmonics. The fr~quency fzO of the additional fundamental oscillation detenmines the spacing o the components in the modulator-output radio-frequency plan. Taking into account the Bessel functions which describe the frequency modulation and the phases thereof, the modulator-output frequency plan can be adjusted to be such that all the xaster lines with a mutual spacing of the frequency fz~ possess the same amplitude.
Furthermore one or t~o of the highest value additional harmonics can be used, by appxopriate adjustment o~ their attenuating elements and phase shift elements, to at least approximately compensate undesi~ed subsidiaxy spectxal lines of the desired frequency p~ttern.
The ~requency-modulated ~requency spectrum which is emitted at the trans~itting end, and in which each radio-frequency carrier is modulated in frequency with theuseful digital informatiQn, contains no amplitude modulation components in its envelope curvet so that non-linear amplifiers can be used at the transmitting and receiving end without any fear of distortion.
The frequency-modulated sum signal received at the antenna A of the receiver E shown in part in Figure 2 is amplified in a receiving amplifier E~, is subsequently converted into a low frequency position in a first receiving mixer stage EUl with the aid of a local oscillation supplied from a local oscillator Ulr and is fed to a selective amplifier SV. The output of the. selective ampli~ier SV feeds the received, converted, frequency-modulate~ signal to be distributed between a number of channels which correspond to . the numbPr of raster fxequencies within the requency field, 20 and in each channel the relevant frequency-modulated carrier is converted to a common intermediate frequency~ For this purpose each of these channels, Kol K l+ to ~n~ and Kl to Kn consists of an input-end intermediate mixer stage U~ which is followed b~ a b~nd pass ~ilter BP and an amplifier V.
For this conversion mutually coherent local oscillations which possess the frequencies ~O~ fl~ to fn-~ a 1- n~
supplied by a common local oscillator arrangement OA. The mutual frequency spacing of the conversion oscillations is equal to the fxequenc~ ~zO o~ the transmitting end additional flln~m~ntal oscillation. ~t their outputs the channels ~O, Kl+ to KntJ ana Kl to Kn are united in a combiner K in such manner that the output su~ signal exhibits an optimum signal-S to-noise ratio. The sum signal for~ed in this way, which is prese~t at the output of the combiner K, is converted into the base band position in a second mixer stage EU2 comprising a local oscillator 02, is subsequently demodulated in a demodulator DN, and the original useful digital signal thus obtained is fed to a data sink DS.
Figure 3 illustrates the spectral diagram at the output of the frequency modulator M illustrated in Figure 1 for an additional fllnd~mental oscillation of the frequency 3 M~z, without any useful signal, and without additional harmonics.
15~ As can be seen from this diagram, a requency pattern is composed of spectral lines mutually spaced by 3 MHz. By suitable adjustment of the frequency ranger for three spectxal lines an identical amplitude is achieved which is followed, i on both sides, by a secondary line attenuated by approximately 25dB. By appropriate adjustment o the frequency range it would also be possiblel apart from the attenuated secondary lines, to produce a frequency pattern comprising two spectral lines spaced by 6 ~z~
The ~requency pattern composed o~ these thxee radio frequencies-of identical amplitude as useful carriers~
and which p~ssesses a total width of 6 MHæ, corresponds for example to approximately half the coherency bandwidths of a - ~. o troposphexic~scatte~ connection. Thus an~ selectlve breaks in level will only suppre~s one of.the radio frequency carriersS whilst the other two remain largely undisturbed.
The signal spectrum illustrated in Figure 4 corresponds to that shown in Figure 3, with the difference that the actual useul signal is likewise fed to the frequency modulator via the adder stage AS in Figure 1. As can be seen from Figure ~, each of the radio-frequency carriers sp~ced by 3 MHz is itself modulated in frequency by the useful signal in the same ~nner.
As has been represented in association with Figures 1 and 2, with the aid of additional harmonics it is possible to increase the number of radio frequency carriers provided in the frequency pattern to 5, 7 or 9, etc. In addition it is possible, with the aid of additional harmonics, to at least approximately suppress undesired secondary lines of the spectrum, such as the frequency spectrum shown in Figure 3 and 4 possesses.
The distxibution of the useful digital signal by means of the special FM-modulation in a system constructed in accordance with the invention, between for example three equally spaced radio frequency carriers, as shown in Figure 3 and 4, results in a po~er reduction of each carrier of appr~ximately 4.8 dB in comparison to the use of one ~ingle caxrier. Taking into account the low energy content of a spectral line (4.8 dB in the case of three radio-frequency carriers) r Figure 5 represents probability curves for the ~ 3;c3 likely ~um ~ useful l~yel. The diagram in ~ ure 5 contains two groups af cuX~eS~ e~ch o~ which lllustrate the likely signal level in dependence upon the channel availability within the limits of 0.1 to 99~. The dash~dotted group of curves WK indicates comparison cur~es of a conventional radio system operating with and without frequency diversityl whereas the solid - line curves referenced 1, 2 and 3 illustrate the results achieved by a system constructed in accordance with the invention.
The probability curve WK, with the FDM
diversity degree D = 1, indicates the course of the Raleigh channel. The corresponding proba~ility curves WK for a diversity degree D = 2 and for a diversity degree D ~ 4 illustrate the corresponding improvement in the recæption conditions when two-fold or four-fold frequency diversity is employed~ Curves 1, 2 and 3 differ from one another only in respect of the spread band widths which is used. In the case of curve 1 the spread band widths amounts to 19 MHz, in the case of curves 2 it amounts to 1~ MHz and in the case of curve 3 it amounts to 6 MHz. As can be seen from the diagram in Figure 5, in the present exampl~, with a frequency pattern comprising three carriers, with 99.9% availability of the system, equivalent FDM diversity degrees of D = 2 to D = 3 can be achieved. The reduction in the fading characteristics in comparison to the Raleigh channel here amounts to 15 to 20 dB, so that in the exemplary embodiment a residual fading of anly 3 to 8 dB is likely. ~hen frequency arxangements comprisin~ ~ore than three radio frequencies are used, the frequency bandwidths of which can also exceed half of one coherency bandwidth,,o~ the s~stem, a further improvement can be achieved ln the reduction of the fading characteristics in comparison to the Raleigh channel.
Claims (5)
1. A digital radio system of the type used in tropo-spheric-scatter and short-wave transmission links, in which means are provided at the transmitting end to impress the useful digital signal upon a radio-frequency carrier by frequency modulation and means provided at the receiving end for demodulation of the received carrier and the provision of a reconstituted data signal for further processing, frequency diversity being employed in order to counter transmission disturbances of the type caused by selected fading resulting from multi-path propagation, the digital signal to be trans-mitted being fed at the transmitting end to a compound frequency changer stage comprising at least two local oscillation frequency sources, one a fundamental oscillation which determines the frequency of the frequency spacing in the compound frequency changer stage, all being fed to the input of a frequency modulator, and at the receiving end the radio-frequency carrier, modulated with the useful signal, being converted back to an equal frequency position in converters by means of mutually coherent local oscillations from a conversion oscillator arrangement, and subsequently fed to a combiner to form a sum signal which exhibits an optimum signal-to-noise ratio.
2. A digital radio system as claimed in Claim 1, in which the modulated carriers of the mixer stage are determined taking into account the Bessel functions and the phase thereof for at least approximately equal amplitudes, and for this purpose means are provided to adjust the amplitude of the fundamental oscillation and the or each harmonic and to adjust the phase-relationship of the harmonics.
3. A digital radio system as claimed in Claim 1 or Claim 2, in which at least one additional harmonic is provided to compensate undesired secondary lines of the compound frequency changer stage.
4. A digital radio system as claimed in Claim 1 or 2, in which the width of the radio-frequency transmitting spectrum is equal to approximately half the occurring coherency bandwidth.
5. A digital radio system as claimed in Claim 1 or Claim 2, in which one additional harmonic is provided to compensate undesired secondary lines of the compound frequency changer stage and in which the width of the radio-frequency transmitting spectrum is equal to approximately half the occurring coherency bandwidth.
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| DE19813121146 DE3121146A1 (en) | 1981-05-27 | 1981-05-27 | DIGITAL RADIO SYSTEM |
| DEP3121146.1 | 1981-05-27 |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CA1198169A true CA1198169A (en) | 1985-12-17 |
Family
ID=6133378
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CA000403823A Expired CA1198169A (en) | 1981-05-27 | 1982-05-25 | Digital radio systems |
Country Status (10)
| Country | Link |
|---|---|
| US (1) | US4628517A (en) |
| EP (1) | EP0065764B1 (en) |
| JP (1) | JPS57199356A (en) |
| AR (1) | AR229991A1 (en) |
| AT (1) | ATE18839T1 (en) |
| AU (1) | AU530445B2 (en) |
| CA (1) | CA1198169A (en) |
| DE (1) | DE3121146A1 (en) |
| NO (1) | NO157880C (en) |
| ZA (1) | ZA823649B (en) |
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-
1981
- 1981-05-27 DE DE19813121146 patent/DE3121146A1/en active Granted
-
1982
- 1982-04-29 AR AR289262A patent/AR229991A1/en active
- 1982-05-12 NO NO821581A patent/NO157880C/en unknown
- 1982-05-19 AT AT82104421T patent/ATE18839T1/en not_active IP Right Cessation
- 1982-05-19 EP EP82104421A patent/EP0065764B1/en not_active Expired
- 1982-05-25 CA CA000403823A patent/CA1198169A/en not_active Expired
- 1982-05-26 JP JP57088145A patent/JPS57199356A/en active Pending
- 1982-05-26 AU AU84195/82A patent/AU530445B2/en not_active Ceased
- 1982-05-26 ZA ZA823649A patent/ZA823649B/en unknown
-
1985
- 1985-09-23 US US06/778,180 patent/US4628517A/en not_active Expired - Fee Related
Also Published As
| Publication number | Publication date |
|---|---|
| NO157880C (en) | 1988-06-01 |
| NO157880B (en) | 1988-02-22 |
| ZA823649B (en) | 1983-03-30 |
| NO821581L (en) | 1982-11-29 |
| JPS57199356A (en) | 1982-12-07 |
| DE3121146A1 (en) | 1983-01-05 |
| US4628517A (en) | 1986-12-09 |
| ATE18839T1 (en) | 1986-04-15 |
| EP0065764A3 (en) | 1983-11-30 |
| AU530445B2 (en) | 1983-07-14 |
| EP0065764A2 (en) | 1982-12-01 |
| AU8419582A (en) | 1982-12-02 |
| DE3121146C2 (en) | 1988-09-08 |
| EP0065764B1 (en) | 1986-03-26 |
| AR229991A1 (en) | 1984-01-31 |
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