CA1273680A - Circuit for extracting carrier signals - Google Patents
Circuit for extracting carrier signalsInfo
- Publication number
- CA1273680A CA1273680A CA000553505A CA553505A CA1273680A CA 1273680 A CA1273680 A CA 1273680A CA 000553505 A CA000553505 A CA 000553505A CA 553505 A CA553505 A CA 553505A CA 1273680 A CA1273680 A CA 1273680A
- Authority
- CA
- Canada
- Prior art keywords
- signal
- bandpass filter
- carrier
- carrier signal
- circuit
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired
Links
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying
- H04L27/22—Demodulator circuits; Receiver circuits
- H04L27/227—Demodulator circuits; Receiver circuits using coherent demodulation
- H04L27/2275—Demodulator circuits; Receiver circuits using coherent demodulation wherein the carrier recovery circuit uses the received modulated signals
- H04L27/2276—Demodulator circuits; Receiver circuits using coherent demodulation wherein the carrier recovery circuit uses the received modulated signals using frequency multiplication or harmonic tracking
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying
- H04L27/20—Modulator circuits; Transmitter circuits
- H04L27/2003—Modulator circuits; Transmitter circuits for continuous phase modulation
- H04L27/2007—Modulator circuits; Transmitter circuits for continuous phase modulation in which the phase change within each symbol period is constrained
- H04L27/2017—Modulator circuits; Transmitter circuits for continuous phase modulation in which the phase change within each symbol period is constrained in which the phase changes are non-linear, e.g. generalized and Gaussian minimum shift keying, tamed frequency modulation
Abstract
ABSTRACT
In circuits for reproducing carriers for continuous phase modulation having a rational modulation index these signals are multiplied in a multiplier for producing a harmonic, with unique phases occurring due to phase addition irrespective of the information to be conveyed. This harmonic is selected by means of a bandpass filter and supplied to a divider for reproducing the carrier signal. However, as the desired phases only occur at certain instants the effects of jitter in the reproduced carrier signal is undesirably high. Jitter suppression is considerably improved by supplying to the bandpass filter only the instantaneous values of the virtually desired phases occurring at the specific instants.
In circuits for reproducing carriers for continuous phase modulation having a rational modulation index these signals are multiplied in a multiplier for producing a harmonic, with unique phases occurring due to phase addition irrespective of the information to be conveyed. This harmonic is selected by means of a bandpass filter and supplied to a divider for reproducing the carrier signal. However, as the desired phases only occur at certain instants the effects of jitter in the reproduced carrier signal is undesirably high. Jitter suppression is considerably improved by supplying to the bandpass filter only the instantaneous values of the virtually desired phases occurring at the specific instants.
Description
~73~
PHN 11.972 1 11.03.1987 Circuit for extracting carrier signals.
The invention relates to a carrier reproducing circuit for extracting the carrier signal from a pulse-coded continuous phase-modulated carrier signal having a rational modulation index, this circuit comprising a clock pulse regenerator, a multiplier having a multi-plication factor N (N = 2, 3, ...) for generating an N harmonic from the modulated carrier signal, a first bandpass filter, coupled to the multiplier for isolating the aforesaid N harmonic and a divider having the dividend N connected to the first bandpass filter.
Such a carrier reproducing circuit for extrac-ting the carrier signal from a pulse-coded continuous phase-modulated carrier signal is ~nown inter alia from the article entitled "Synchroni~ation properties of continuous phase modulation" by J. Aulin and C~Eo Sundberg, published in the "Conference Papers" of "Globecom 82, Global Telecommunication Conference, Mi.ami, 29th November - 2nd December 1982.
Continuous phase modulation is used because the modulated carrier signals have a constant ampli-tude enabling non-linear amplification, and because they usually have a small bandwidth, This modulation category comprises among others Tamed Frequency Modu-lation (TFM), Quadrivalent Three-bit Correlated Cosinus-oidal Modulation ~Q3RC) and Correlative Phase ShiftKeying (CORPSK).
It has appeared tha-t a~large jitter value commonly occurs in a carrier signal extracted in the way described hereinbefore.
The invention has for its object to strongly reduce in a simple manner the jitter effect occurring when reproducing a carrier signal from a continous ~' 3~;8~
PHN 11.972 2 11.03.19~7 :, , phase-modulated carrier signal.
The circuit for extracting carrier signals in accordance with the invention is characteri~ed in -that between the multiplier and the first bandpass filter a sampling circuit is inserted connected to the clock pulse regenerator for instantaneous sampling of the N
harmonic under the control of a clock pulse signal originating from the clock pulse regenerator at no less than one predetermined sampling point per symbol time T of the data signal, and for conveying these in-stantaneously sampled signal values to the first band-pass filter only.
It should be noted here t~at from the United States Patent 3,835,404 a carrier reproducing circuit is known comprising a multiplier, a sampli~ circuit connected thereto for sampling the multiplied carrier signal under the control of a clock pulse and a cas-cade arrangement composed of a bandpass filter and a divider connected to the sampling circuit. However, a carrier reproducing circuit for PSK signals is dis-cussed wherein the jitter due to phase displacementsin the carrier signal occurring at bi-t transitions is avoided by sampling by clock pulses having a pulse-width which is smaller than the distance between -the successive phase displacements in the modulated carrier signal but having as large a finite width as possible.
In contradistinction thereto it is essential when extracting the carrier signal from a continuous phase-modulated carrier signal in accordance wi-th the invention that instantaneous sampling at predetermined sampling points be achieved for obtaining as reliable a reproduced carrier signal as possible.
The invention and its advantages will further be explained with reference to the embodiments shown in the drawing, wherein corresponding elements in tha Figures are indicated by identical reference numsrals and wherein:
Figure 1: shows a bloc~ diagram of a receiver 3~
, PHN 11.972 3 11.03.1987 comprising a carrier reproducing circuit for continuous phase-modulated signals having a rational modulation index in accordance with the invention, Figure 2a: shows the impulse response and Figure 2b: shows the waveform of a 2~C-signal, Figure 3a: shows the impulse response and Figure 3b: shows the waveform for CORPSK (2-3, 1 + D) and duebinary CP~I with h =
O,5 and Figure 4a: shows the impulse response and Figure 4b: shows the waveform for TFM and TFSK, respectivelyO
With the receiver comprising a carrier-repro-ducing circuit 10, shown in Figure l, it is possible 15 to extract in a highly reliable way a continuous phase-modulated carrier signal (CPM-signal) applied to input-terminal 1 and having a rational modulation index h such that the resulting carrier has a small phase jitter.
Before embarking on the explanation of the carrier re-producing circuit, the struc-ture of such a CPM-signal is further elucidated.
An information signal to be -transferred digital-ly, represented by a series (am) of m-nary digi-tal symbols, 25 (a ) = .. a 2,a_1~ao'al'a2~ n (1) with am = ~(2n~1) and n=0,1,2,...etc.
can be represented as a function of time by a(t) = ~ amp(t-mT~ (2) with T represen-ting the duration of the digital symbols and p(t) representing a rectangular pulse of a length of T.
Before transferring such signals they are pre-ferably modulated in that the modulated carrier signal has a constant amplitude. The major advantage of such a carrier signal is the fact that non-linear signal processing such as non-linear amplification for obtaining a high efficiency, can be used without affecting -the information contained in the signal 3~,~3(3 PHN 11.972 1~ 11.03,1987 Each digital modula-tion having a cons-tant ampli-tude can be written as:
u(t) = cos(~ct + ~(t)) (3) wherein ~c represents the angular frequency of the carrier signal and ~(t) represents the phase as a function of time.
If ~ ~t) is varied as a function of a(-t) the following equation will be obtained:
~(t) ~ ~{a(t)) (4) In Phase Shift Keying (PSK) ~ (t) is kept constant over the symbol time T and changed abruptly at the symbol transitions.
However, there are also types of modulation such as Continuous Phase Frequency Shif-t Keying (CPFSK), for which the following condition holds:
d ~ (t)/d(t) = K-a(t) (5) wherein K is a constant. With Con-tinuous Phase Fre quency Shift Keying the detection process for obtaining a better S/N ra-tio can be spread out over more than one symbol interval.
Examples of CPFSK are Minimum Shift Keying (MSK) and Sinusoidal Frequency Shift Keying (SFSK). MSK
is a modulation entailing a linear phase shift o~`
~ ~/2 per symbol time, which is denoted by the modu--lation index h = O.5 wi-th h being defined as -the number -of ~ radians which the phase is changed per symbol time T.
With SFSK not only the phase but also the first derivative of the phase, so the frequency, is continous. This improves side-band suppression.
I~ the phase shift with CPFSK is made such that smooth phase transitions between s~mbol inter-vals are realized, the phase change will no longer be constant over a symbol interval and one will commonly refer thereto as Continuous Phase Modulation (CPM).
In view of the ever occurring phase changes over each symbol time, a special carrier reproducing circuit, for example as shown in Figure 1~ has -to be used for ~ ~ ~t~3 ~
PHN 11.972 5 11.03.1987 extracting the carrier signal from a received CPM-signal.
Examples of CPMs are Raised Cosine Modula-tion (RCM), having a self-explanatory name and the category of Correlative Phase Modulation (CORPM).
To achieve a further smoothing of the phase shift when using CORPM, the phase change in a symbol time also depends on the information of one or a plurality of preceding symbol times. Known CORPMs are the Tamed Frequency Modulation (TFM), Correlative Phass Shift Keying (CORPSK) and Gaussian Modified Shift Keying (GMSK).
Of all CPM-types only those types are of im-portance to the invention wherein at fixed points of time substantially fixed phase values occur which can 15 be denoted as a whole fraction of 2 ~ , for example
PHN 11.972 1 11.03.1987 Circuit for extracting carrier signals.
The invention relates to a carrier reproducing circuit for extracting the carrier signal from a pulse-coded continuous phase-modulated carrier signal having a rational modulation index, this circuit comprising a clock pulse regenerator, a multiplier having a multi-plication factor N (N = 2, 3, ...) for generating an N harmonic from the modulated carrier signal, a first bandpass filter, coupled to the multiplier for isolating the aforesaid N harmonic and a divider having the dividend N connected to the first bandpass filter.
Such a carrier reproducing circuit for extrac-ting the carrier signal from a pulse-coded continuous phase-modulated carrier signal is ~nown inter alia from the article entitled "Synchroni~ation properties of continuous phase modulation" by J. Aulin and C~Eo Sundberg, published in the "Conference Papers" of "Globecom 82, Global Telecommunication Conference, Mi.ami, 29th November - 2nd December 1982.
Continuous phase modulation is used because the modulated carrier signals have a constant ampli-tude enabling non-linear amplification, and because they usually have a small bandwidth, This modulation category comprises among others Tamed Frequency Modu-lation (TFM), Quadrivalent Three-bit Correlated Cosinus-oidal Modulation ~Q3RC) and Correlative Phase ShiftKeying (CORPSK).
It has appeared tha-t a~large jitter value commonly occurs in a carrier signal extracted in the way described hereinbefore.
The invention has for its object to strongly reduce in a simple manner the jitter effect occurring when reproducing a carrier signal from a continous ~' 3~;8~
PHN 11.972 2 11.03.19~7 :, , phase-modulated carrier signal.
The circuit for extracting carrier signals in accordance with the invention is characteri~ed in -that between the multiplier and the first bandpass filter a sampling circuit is inserted connected to the clock pulse regenerator for instantaneous sampling of the N
harmonic under the control of a clock pulse signal originating from the clock pulse regenerator at no less than one predetermined sampling point per symbol time T of the data signal, and for conveying these in-stantaneously sampled signal values to the first band-pass filter only.
It should be noted here t~at from the United States Patent 3,835,404 a carrier reproducing circuit is known comprising a multiplier, a sampli~ circuit connected thereto for sampling the multiplied carrier signal under the control of a clock pulse and a cas-cade arrangement composed of a bandpass filter and a divider connected to the sampling circuit. However, a carrier reproducing circuit for PSK signals is dis-cussed wherein the jitter due to phase displacementsin the carrier signal occurring at bi-t transitions is avoided by sampling by clock pulses having a pulse-width which is smaller than the distance between -the successive phase displacements in the modulated carrier signal but having as large a finite width as possible.
In contradistinction thereto it is essential when extracting the carrier signal from a continuous phase-modulated carrier signal in accordance wi-th the invention that instantaneous sampling at predetermined sampling points be achieved for obtaining as reliable a reproduced carrier signal as possible.
The invention and its advantages will further be explained with reference to the embodiments shown in the drawing, wherein corresponding elements in tha Figures are indicated by identical reference numsrals and wherein:
Figure 1: shows a bloc~ diagram of a receiver 3~
, PHN 11.972 3 11.03.1987 comprising a carrier reproducing circuit for continuous phase-modulated signals having a rational modulation index in accordance with the invention, Figure 2a: shows the impulse response and Figure 2b: shows the waveform of a 2~C-signal, Figure 3a: shows the impulse response and Figure 3b: shows the waveform for CORPSK (2-3, 1 + D) and duebinary CP~I with h =
O,5 and Figure 4a: shows the impulse response and Figure 4b: shows the waveform for TFM and TFSK, respectivelyO
With the receiver comprising a carrier-repro-ducing circuit 10, shown in Figure l, it is possible 15 to extract in a highly reliable way a continuous phase-modulated carrier signal (CPM-signal) applied to input-terminal 1 and having a rational modulation index h such that the resulting carrier has a small phase jitter.
Before embarking on the explanation of the carrier re-producing circuit, the struc-ture of such a CPM-signal is further elucidated.
An information signal to be -transferred digital-ly, represented by a series (am) of m-nary digi-tal symbols, 25 (a ) = .. a 2,a_1~ao'al'a2~ n (1) with am = ~(2n~1) and n=0,1,2,...etc.
can be represented as a function of time by a(t) = ~ amp(t-mT~ (2) with T represen-ting the duration of the digital symbols and p(t) representing a rectangular pulse of a length of T.
Before transferring such signals they are pre-ferably modulated in that the modulated carrier signal has a constant amplitude. The major advantage of such a carrier signal is the fact that non-linear signal processing such as non-linear amplification for obtaining a high efficiency, can be used without affecting -the information contained in the signal 3~,~3(3 PHN 11.972 1~ 11.03,1987 Each digital modula-tion having a cons-tant ampli-tude can be written as:
u(t) = cos(~ct + ~(t)) (3) wherein ~c represents the angular frequency of the carrier signal and ~(t) represents the phase as a function of time.
If ~ ~t) is varied as a function of a(-t) the following equation will be obtained:
~(t) ~ ~{a(t)) (4) In Phase Shift Keying (PSK) ~ (t) is kept constant over the symbol time T and changed abruptly at the symbol transitions.
However, there are also types of modulation such as Continuous Phase Frequency Shif-t Keying (CPFSK), for which the following condition holds:
d ~ (t)/d(t) = K-a(t) (5) wherein K is a constant. With Con-tinuous Phase Fre quency Shift Keying the detection process for obtaining a better S/N ra-tio can be spread out over more than one symbol interval.
Examples of CPFSK are Minimum Shift Keying (MSK) and Sinusoidal Frequency Shift Keying (SFSK). MSK
is a modulation entailing a linear phase shift o~`
~ ~/2 per symbol time, which is denoted by the modu--lation index h = O.5 wi-th h being defined as -the number -of ~ radians which the phase is changed per symbol time T.
With SFSK not only the phase but also the first derivative of the phase, so the frequency, is continous. This improves side-band suppression.
I~ the phase shift with CPFSK is made such that smooth phase transitions between s~mbol inter-vals are realized, the phase change will no longer be constant over a symbol interval and one will commonly refer thereto as Continuous Phase Modulation (CPM).
In view of the ever occurring phase changes over each symbol time, a special carrier reproducing circuit, for example as shown in Figure 1~ has -to be used for ~ ~ ~t~3 ~
PHN 11.972 5 11.03.1987 extracting the carrier signal from a received CPM-signal.
Examples of CPMs are Raised Cosine Modula-tion (RCM), having a self-explanatory name and the category of Correlative Phase Modulation (CORPM).
To achieve a further smoothing of the phase shift when using CORPM, the phase change in a symbol time also depends on the information of one or a plurality of preceding symbol times. Known CORPMs are the Tamed Frequency Modulation (TFM), Correlative Phass Shift Keying (CORPSK) and Gaussian Modified Shift Keying (GMSK).
Of all CPM-types only those types are of im-portance to the invention wherein at fixed points of time substantially fixed phase values occur which can 15 be denoted as a whole fraction of 2 ~ , for example
2 ~ /2 with n = ~ 2, These types of modulations will further be indicated as CPM with a rational modulation index h.
If a carrier signal modulated thus is applied to input terminal 1 of the receiver comprising the carrier-reproducing circuit 10 represented in ~igure 1, thesignal is applied to a multiplier 3 in the conventional manner after being ~iltered in a band-pass filter 2 which will further be referred to as a -third bandpass filter. Such a multiplier 3 comprises a non~linear elemen-t by means of which the modulated carrier signal, having a factor M and preferably being equal to 2/h, is multiplied for achieving a desired harmonic. ~s a result of the multiplication the phase variations of the modulated carrier signal end up in the same phase (modulo 2 ~ ). In known carrier-reproducing circuits for CPM modulated signals the thus obtained signal is directly applied to a first bandpass filter 4 having a small bandwidth, for example in the order of 1/1oOth fIN, where fIN represents the frequency of the received signal, for elimina-ting all undesired harmonics, after which the desired harmonic of the carrier signal is divided in a divider 5 having dividend N. The thus 73~
PH\ 1 .972 6 11~03.1987 reproduced carrier signal is applied to a coherent detector 6 likewise connected to the third wide-band filter 2 for coherent demodulation of the filtered input signal.
Figures 2a to 4b show several examples of CPM-signals having a substantially rational modulation index. Figure 2a shows therein the impulse response g(t) of a pulse applied to a modulator (not shown) in a transmitter for RC-signals. The time is plotted along the horizontal axis in units of the symbol time T and the amplitude is plotted along the vertical axis in units of ~ . This Figure shows that the impulse res-ponse for RC-modulated signals repr.esented therein has a length of 2T and is therefore a CORPM-signal indicated by 2RC. Figure 2b depicts in a waveform the phase shift of a carrier signal continuously phase-modulated by means of this impulse response. Such a waveform represents any occurring phase variations as a function of time of a carrier signal modulated by an arbitrary data signal. Along the vertical axis is plotted the phase in units of whereas along the horizontal axis the time is plotted in units of symbol time T.
As is shown in these Figures the phase at the instants mT, with m = O, 1, 2, ..., has a specific value equal to Gne of the values nH~ , with n = O, + 1, + 2, ... etc. The fact that the phase substantially has fixed values at the afore mentioned instants is caused by the surface under the impulse response curve g(t) and hence the modulation index having the value equal to h due to -the dimensioning of the premodulation filter, so that the phase per -time T can exactly change by the values of h ~r . In most types of CPM modulation the phases at the instants mT have the constant unique values of (O + 2 ~ n) only after multiplication of the modulated carrier signal by -the factor 2/h in the mul-tiplier 3. An example of an exception to this is formed by TFM, wherein a substantially constant unique value PHN 11.972 7 11.03.1987 ((+2n~ r ) occurs not only with a fac-tor eight but also with a factor four, as will be explained herein-after t Figure 3a shows the impulse responses g(t) and Figure 3b shows the relevant waveform for CORPSX (2-3, 1+~) in solid lines and for duobinary CPM in dashed lines. In the indication (2-3, 1~D) the numeral 2 points out that the information signal applied to the premodu-lation filter is binary, the numeral 3 that the output signal of the premodulation filter is trinary for modu~
lating the carrier signal wi-th three different phase values, and 1+D -that the successive information bits are correlated because in the premodulation filter the instantaneous standardized information bit, indicated by 1, has to be added to the preceding information bit delayed over a period time T indicated by the D
of DelayO
In Figure 3a the area underneath the impulse response curve g(t) has the value of 1/2 so that all branches of the waveform pass through the fixed phase points n ~/2 at the instants nT. Multiplication in multiplier 3 (Figure 1) by 2/h = 4 brings the phase at the~forementioned instants back to O + 2 ~ n in the desired harmonic.
As a last example Figure 4a shows the impulse response g(t) and Figure 4b shows the associated wave-form for TFM in solid lines whilst for TFSK (Tamed Frequency Shift Keying) the dashed lines are used~
Here too the phase of the carrier signal turns out to have exact values at the end of the symbol intervals, in this case equal to n ~/4. Consequently, a multipli-cation by a factor 8 is required in the multiplier (Figure 1). However, Figure 4b shows that in the centre of the symbol intervals the phases always turn out to be close to the values of ~/4 + n ~/2, where n is an integer. Multiplying this signal by a factor 4 in the multiplier 3 will now suffice for achieving the sub~an-tially fixed values ~ ~ 2 ~ n at the aforementioned
If a carrier signal modulated thus is applied to input terminal 1 of the receiver comprising the carrier-reproducing circuit 10 represented in ~igure 1, thesignal is applied to a multiplier 3 in the conventional manner after being ~iltered in a band-pass filter 2 which will further be referred to as a -third bandpass filter. Such a multiplier 3 comprises a non~linear elemen-t by means of which the modulated carrier signal, having a factor M and preferably being equal to 2/h, is multiplied for achieving a desired harmonic. ~s a result of the multiplication the phase variations of the modulated carrier signal end up in the same phase (modulo 2 ~ ). In known carrier-reproducing circuits for CPM modulated signals the thus obtained signal is directly applied to a first bandpass filter 4 having a small bandwidth, for example in the order of 1/1oOth fIN, where fIN represents the frequency of the received signal, for elimina-ting all undesired harmonics, after which the desired harmonic of the carrier signal is divided in a divider 5 having dividend N. The thus 73~
PH\ 1 .972 6 11~03.1987 reproduced carrier signal is applied to a coherent detector 6 likewise connected to the third wide-band filter 2 for coherent demodulation of the filtered input signal.
Figures 2a to 4b show several examples of CPM-signals having a substantially rational modulation index. Figure 2a shows therein the impulse response g(t) of a pulse applied to a modulator (not shown) in a transmitter for RC-signals. The time is plotted along the horizontal axis in units of the symbol time T and the amplitude is plotted along the vertical axis in units of ~ . This Figure shows that the impulse res-ponse for RC-modulated signals repr.esented therein has a length of 2T and is therefore a CORPM-signal indicated by 2RC. Figure 2b depicts in a waveform the phase shift of a carrier signal continuously phase-modulated by means of this impulse response. Such a waveform represents any occurring phase variations as a function of time of a carrier signal modulated by an arbitrary data signal. Along the vertical axis is plotted the phase in units of whereas along the horizontal axis the time is plotted in units of symbol time T.
As is shown in these Figures the phase at the instants mT, with m = O, 1, 2, ..., has a specific value equal to Gne of the values nH~ , with n = O, + 1, + 2, ... etc. The fact that the phase substantially has fixed values at the afore mentioned instants is caused by the surface under the impulse response curve g(t) and hence the modulation index having the value equal to h due to -the dimensioning of the premodulation filter, so that the phase per -time T can exactly change by the values of h ~r . In most types of CPM modulation the phases at the instants mT have the constant unique values of (O + 2 ~ n) only after multiplication of the modulated carrier signal by -the factor 2/h in the mul-tiplier 3. An example of an exception to this is formed by TFM, wherein a substantially constant unique value PHN 11.972 7 11.03.1987 ((+2n~ r ) occurs not only with a fac-tor eight but also with a factor four, as will be explained herein-after t Figure 3a shows the impulse responses g(t) and Figure 3b shows the relevant waveform for CORPSX (2-3, 1+~) in solid lines and for duobinary CPM in dashed lines. In the indication (2-3, 1~D) the numeral 2 points out that the information signal applied to the premodu-lation filter is binary, the numeral 3 that the output signal of the premodulation filter is trinary for modu~
lating the carrier signal wi-th three different phase values, and 1+D -that the successive information bits are correlated because in the premodulation filter the instantaneous standardized information bit, indicated by 1, has to be added to the preceding information bit delayed over a period time T indicated by the D
of DelayO
In Figure 3a the area underneath the impulse response curve g(t) has the value of 1/2 so that all branches of the waveform pass through the fixed phase points n ~/2 at the instants nT. Multiplication in multiplier 3 (Figure 1) by 2/h = 4 brings the phase at the~forementioned instants back to O + 2 ~ n in the desired harmonic.
As a last example Figure 4a shows the impulse response g(t) and Figure 4b shows the associated wave-form for TFM in solid lines whilst for TFSK (Tamed Frequency Shift Keying) the dashed lines are used~
Here too the phase of the carrier signal turns out to have exact values at the end of the symbol intervals, in this case equal to n ~/4. Consequently, a multipli-cation by a factor 8 is required in the multiplier (Figure 1). However, Figure 4b shows that in the centre of the symbol intervals the phases always turn out to be close to the values of ~/4 + n ~/2, where n is an integer. Multiplying this signal by a factor 4 in the multiplier 3 will now suffice for achieving the sub~an-tially fixed values ~ ~ 2 ~ n at the aforementioned
3~;~3V
PHN 1l.972 8 11.03.1987 sampling points (1/2 + m)T in the desired harmonic sig-nal.
Despite the fact that the phases at the afore-mentioned sampling points do not exactly have the values of ~/4 + n ~ /2, with respect to the fixed phase points at the sampling points mT, this is advan-tageous in that a reliable carrier reproduction is feasible by a mere multiplication by a factor L~.
For CPM-signals having a rational modulation index it may be concluded from the aforeshown examples that by a multiplication by an integer the phases of the carrier signal are incremented such that at cer-tain sampling points a single vir-tually fixed phase value occurs in the desired harmonic signal, ~or example O + 2 ~ n or ~ 2 ~ n, that is to say a carrier phase irrespective of the symbol pattern of a data series.
Extracting the carrier signal by supplying the output signal of the multiplier 3 directly to the narrow-band first bandpass filter 4 in the conventional way, has a sub-optimal result due to the not insigni-ficant jittor in the reproduced carrier signal. This jitter effect occurs as mary elements causing distur-bance occur in the signal after the multiplier 3 in addition to the desired phase values at the aforesaid sampling points.
To reduce this jitter e,fect the carrier repro-ducing circuit 10 comprises a sampling means 7 inserted between the multiplier 3 and the first bandpass fil-ter
PHN 1l.972 8 11.03.1987 sampling points (1/2 + m)T in the desired harmonic sig-nal.
Despite the fact that the phases at the afore-mentioned sampling points do not exactly have the values of ~/4 + n ~ /2, with respect to the fixed phase points at the sampling points mT, this is advan-tageous in that a reliable carrier reproduction is feasible by a mere multiplication by a factor L~.
For CPM-signals having a rational modulation index it may be concluded from the aforeshown examples that by a multiplication by an integer the phases of the carrier signal are incremented such that at cer-tain sampling points a single vir-tually fixed phase value occurs in the desired harmonic signal, ~or example O + 2 ~ n or ~ 2 ~ n, that is to say a carrier phase irrespective of the symbol pattern of a data series.
Extracting the carrier signal by supplying the output signal of the multiplier 3 directly to the narrow-band first bandpass filter 4 in the conventional way, has a sub-optimal result due to the not insigni-ficant jittor in the reproduced carrier signal. This jitter effect occurs as mary elements causing distur-bance occur in the signal after the multiplier 3 in addition to the desired phase values at the aforesaid sampling points.
To reduce this jitter e,fect the carrier repro-ducing circuit 10 comprises a sampling means 7 inserted between the multiplier 3 and the first bandpass fil-ter
4, which sampling means is controlled by a clock signal coming from a clock signal regenerator 8. This clock signal regenerator 8 is connected to the wide band filter 2 for regenerating an accurate clock signal in the known manner from tne signal produced by the wide band filter 2. Such a clock signal regenerator is, for example, described in the aforementioned article en-titled "Synchronization properties of continuous phase modulation'l by T. Aulin and C.E. Sundberg, published in the Conference Papers of Globecom 82, Global Tele-~ ~7~
PHN 11.972 9 11.03.1~87 communications Conference, Miami, 29 November - 2 December 1982.
The clock signal regenerator 8 further com-prises a delay means, which is not shown, (for example a delay line) having such a delay that the delayed clock pulses occur at the sampling point desired for a spe-cific CPM signal in each symbol interval. If the re-ceiver has to be suitable for receiving several types of CPM signals, a single adjustable delay means can be used to advantage rather than several switchable delay means.
As the phase of the modulated carrier signal has the desired value only at one or in some cases at two points per symbol interval, it is essential that the phase be sampled only at these points. This implies that sampling by means of a sampling pulse wider than an instantaneous sampling pulse will have a detrimental effect on the accuracy of the reproduced carrier sig-nal.
A further improvement is obtained by inserting a relatively wide second bandpass filter 9, preferably having a bandwidth in the order of fIN, between the multiplier 3 and the sampling means 7, to isola-te the spectrum of the desired harmonic.
The improvement of a single C.P.M. signal having a rational modulation index, more specifically a TFM-signal, achieved by sampling will now further be explained with reference to a table showing computer simulations.
In the first column of the table is shown the S/N-ratio of the TFM-signal applied to the reproducing circuit of Figure 1.
The three remaining columns of the table show the square root of the mean square value of the phase error ~ 0 of the reproduced carrier signal over the last 136 da-ta symbols of 156 received data symbols as well as the acquisition time TaCq of the receiver, ex-~ ~73~
PHN 11.972 10 11.03.1987 pressed in symbol times T, assuming acquisition if thephase error is smaller than 5 . More specifically, the first column of these three shows the aforementioned values for a multiplication factor N=4, without sampling the second column shows the values for a multiplication factor N=4 with instantaneous sampling in the centre of the symbol intervals and the third column shows the valu~s-for a multiplication factor N=8 with instan-taneous sampling at the end of the symbol intervals.
_ - _ S/N ~ 0rms(deg)/Tacq(symbols) (dB) wi-thout sampling with sampling with sampling N=4 N=4 N=8 _ . ~ .
1540 0.5/7 0.5/3 0.1/5 16 1.6/2 -I.~/6 0.6/2 13 2.~/3 1.4/5 1.1/2 3.6/10 1.9/7 6.3/7 7 4.9/12 3.3/~
Table fvr TFM signal From this table it can be concluded that with ins-tan-taneous sampling in -the cen-tre of the bit interval (N=4) a considerable improvement in suppressing phase jitter is achieved for TFM-signals compared with the cases where no sampling is used. More specifically so with S/~ ratios which are most important in practice. At a S/N-ratio of 10 dB, for example, the improved phase jitter suppression is even 6 dB. With instantaneous sampling at the end (N=8) of the symbol intervals, where the phase is exactly equal to a multiple of ~/4 9 the jitter suppression is far better than with instan taneous sampling in the centre (N=4) of -the symbol intervals, more specifically, up to a S/N ratio better than approximately 12 dB. However, at a S/N ratio of 10 dB the high multiplication factor starts taking i-ts toll and the phase jitter in the reproduced carrier signal will rise rapidly.
73~
PHN 11.972 11 11.03.1987 Indeed, for prac-tical values of the S/N ratio the multiplication factor 4 with centre-sampling is to be preferred. The above-mentioned example will have shown that improvements similar to those shown for TFM signals will likewise occur for other CPM-signals having a rational modula-tlon index.
PHN 11.972 9 11.03.1~87 communications Conference, Miami, 29 November - 2 December 1982.
The clock signal regenerator 8 further com-prises a delay means, which is not shown, (for example a delay line) having such a delay that the delayed clock pulses occur at the sampling point desired for a spe-cific CPM signal in each symbol interval. If the re-ceiver has to be suitable for receiving several types of CPM signals, a single adjustable delay means can be used to advantage rather than several switchable delay means.
As the phase of the modulated carrier signal has the desired value only at one or in some cases at two points per symbol interval, it is essential that the phase be sampled only at these points. This implies that sampling by means of a sampling pulse wider than an instantaneous sampling pulse will have a detrimental effect on the accuracy of the reproduced carrier sig-nal.
A further improvement is obtained by inserting a relatively wide second bandpass filter 9, preferably having a bandwidth in the order of fIN, between the multiplier 3 and the sampling means 7, to isola-te the spectrum of the desired harmonic.
The improvement of a single C.P.M. signal having a rational modulation index, more specifically a TFM-signal, achieved by sampling will now further be explained with reference to a table showing computer simulations.
In the first column of the table is shown the S/N-ratio of the TFM-signal applied to the reproducing circuit of Figure 1.
The three remaining columns of the table show the square root of the mean square value of the phase error ~ 0 of the reproduced carrier signal over the last 136 da-ta symbols of 156 received data symbols as well as the acquisition time TaCq of the receiver, ex-~ ~73~
PHN 11.972 10 11.03.1987 pressed in symbol times T, assuming acquisition if thephase error is smaller than 5 . More specifically, the first column of these three shows the aforementioned values for a multiplication factor N=4, without sampling the second column shows the values for a multiplication factor N=4 with instantaneous sampling in the centre of the symbol intervals and the third column shows the valu~s-for a multiplication factor N=8 with instan-taneous sampling at the end of the symbol intervals.
_ - _ S/N ~ 0rms(deg)/Tacq(symbols) (dB) wi-thout sampling with sampling with sampling N=4 N=4 N=8 _ . ~ .
1540 0.5/7 0.5/3 0.1/5 16 1.6/2 -I.~/6 0.6/2 13 2.~/3 1.4/5 1.1/2 3.6/10 1.9/7 6.3/7 7 4.9/12 3.3/~
Table fvr TFM signal From this table it can be concluded that with ins-tan-taneous sampling in -the cen-tre of the bit interval (N=4) a considerable improvement in suppressing phase jitter is achieved for TFM-signals compared with the cases where no sampling is used. More specifically so with S/~ ratios which are most important in practice. At a S/N-ratio of 10 dB, for example, the improved phase jitter suppression is even 6 dB. With instantaneous sampling at the end (N=8) of the symbol intervals, where the phase is exactly equal to a multiple of ~/4 9 the jitter suppression is far better than with instan taneous sampling in the centre (N=4) of -the symbol intervals, more specifically, up to a S/N ratio better than approximately 12 dB. However, at a S/N ratio of 10 dB the high multiplication factor starts taking i-ts toll and the phase jitter in the reproduced carrier signal will rise rapidly.
73~
PHN 11.972 11 11.03.1987 Indeed, for prac-tical values of the S/N ratio the multiplication factor 4 with centre-sampling is to be preferred. The above-mentioned example will have shown that improvements similar to those shown for TFM signals will likewise occur for other CPM-signals having a rational modula-tlon index.
Claims (4)
PROPERTY OR PRIVILEGE IS CLAIMED ARE DEFINED AS FOLLOWS:
1. A carrier reproducing circuit for extracting the carrier signal from a pulse-coded continuous phase-modulated carrier signal having a rational modulation index, this circuit comprising a clock pulse regenerator, a multiplier having a multi-plication factor N(N = 2, 3, ...) for generating an Nth harmonic from the modulated carrier signal, a first bandpass filter coupled to the multiplier for isolating the aforesaid Nth harmonic and a divider having the divided N connected to the first bandpass filter, characterized in that between the multiplier and the first bandpass filter a sampling circuit is inserted connected to the clock pulse regenerator for instantaneous sampling of the Nth harmonic under the control of a clock pulse signal originating from the clock pulse regenerator at no less than one predetermined sampling point per symbol time T of the data signal, and for conveying these instantaneously sampled signal values to the first bandpass filter only.
2. A carrier producing circuit as claimed in Claim 1, characterized in that a second bandpass filter is inserted between the multiplier and the sampling arrangement, this band filter having a bandwidth exceeding by far the bandwidth of the first bandpass filter.
3. A carrier reproducing circuit as claimed in Claim 1, characterized in that the clock pulse regenerator comprises an adjustable delay means for being capable of reproducing a carrier wave for any type of continuous phase-modulated carrier signal having a rational modulation index.
4. A receiver comprising a carrier reproducing circuit as claimed in Claim 1, 2 or 3.
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| NL8603110 | 1986-12-08 | ||
| NL8603110A NL8603110A (en) | 1986-12-08 | 1986-12-08 | SWITCH FOR RECOVERING A CARRIER. |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CA1273680A true CA1273680A (en) | 1990-09-04 |
Family
ID=19848962
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CA000553505A Expired CA1273680A (en) | 1986-12-08 | 1987-12-04 | Circuit for extracting carrier signals |
Country Status (8)
| Country | Link |
|---|---|
| US (1) | US4890302A (en) |
| EP (1) | EP0273504B1 (en) |
| JP (1) | JP2541588B2 (en) |
| AU (1) | AU8214187A (en) |
| CA (1) | CA1273680A (en) |
| DE (1) | DE3784675T2 (en) |
| DK (1) | DK168843B1 (en) |
| NL (1) | NL8603110A (en) |
Families Citing this family (32)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US5001724A (en) * | 1989-01-13 | 1991-03-19 | Hewlett-Packard Company | Method and apparatus for measuring phase accuracy and amplitude profile of a continuous-phase-modulated signal |
| JP2679889B2 (en) * | 1990-07-19 | 1997-11-19 | 株式会社テック | Wireless communication device and reception control method of the device |
| FR2727813B1 (en) * | 1994-12-02 | 1997-01-10 | Alcatel Telspace | DEVICE FOR DETECTING THE PRESENCE OR ABSENCE OF A DIGITALLY MODULATED CARRIER, CORRESPONDING RECEIVER AND METHOD |
| JP3497672B2 (en) * | 1996-09-18 | 2004-02-16 | 株式会社東芝 | Adaptive antenna and multi-carrier wireless communication system |
| FI974506A0 (en) * | 1997-12-12 | 1997-12-12 | Nokia Telecommunications Oy | Demoduleringsfoerfarande och demodulator |
| US6091940A (en) | 1998-10-21 | 2000-07-18 | Parkervision, Inc. | Method and system for frequency up-conversion |
| US6061551A (en) | 1998-10-21 | 2000-05-09 | Parkervision, Inc. | Method and system for down-converting electromagnetic signals |
| US6694128B1 (en) | 1998-08-18 | 2004-02-17 | Parkervision, Inc. | Frequency synthesizer using universal frequency translation technology |
| US7515896B1 (en) | 1998-10-21 | 2009-04-07 | Parkervision, Inc. | Method and system for down-converting an electromagnetic signal, and transforms for same, and aperture relationships |
| US6542722B1 (en) | 1998-10-21 | 2003-04-01 | Parkervision, Inc. | Method and system for frequency up-conversion with variety of transmitter configurations |
| US6813485B2 (en) | 1998-10-21 | 2004-11-02 | Parkervision, Inc. | Method and system for down-converting and up-converting an electromagnetic signal, and transforms for same |
| US7236754B2 (en) | 1999-08-23 | 2007-06-26 | Parkervision, Inc. | Method and system for frequency up-conversion |
| US6370371B1 (en) | 1998-10-21 | 2002-04-09 | Parkervision, Inc. | Applications of universal frequency translation |
| US6061555A (en) | 1998-10-21 | 2000-05-09 | Parkervision, Inc. | Method and system for ensuring reception of a communications signal |
| US6560301B1 (en) | 1998-10-21 | 2003-05-06 | Parkervision, Inc. | Integrated frequency translation and selectivity with a variety of filter embodiments |
| US6049706A (en) | 1998-10-21 | 2000-04-11 | Parkervision, Inc. | Integrated frequency translation and selectivity |
| US7039372B1 (en) | 1998-10-21 | 2006-05-02 | Parkervision, Inc. | Method and system for frequency up-conversion with modulation embodiments |
| US6704549B1 (en) | 1999-03-03 | 2004-03-09 | Parkvision, Inc. | Multi-mode, multi-band communication system |
| US6704558B1 (en) | 1999-01-22 | 2004-03-09 | Parkervision, Inc. | Image-reject down-converter and embodiments thereof, such as the family radio service |
| US6853690B1 (en) | 1999-04-16 | 2005-02-08 | Parkervision, Inc. | Method, system and apparatus for balanced frequency up-conversion of a baseband signal and 4-phase receiver and transceiver embodiments |
| US6879817B1 (en) | 1999-04-16 | 2005-04-12 | Parkervision, Inc. | DC offset, re-radiation, and I/Q solutions using universal frequency translation technology |
| US7065162B1 (en) | 1999-04-16 | 2006-06-20 | Parkervision, Inc. | Method and system for down-converting an electromagnetic signal, and transforms for same |
| US7110444B1 (en) | 1999-08-04 | 2006-09-19 | Parkervision, Inc. | Wireless local area network (WLAN) using universal frequency translation technology including multi-phase embodiments and circuit implementations |
| US7693230B2 (en) | 1999-04-16 | 2010-04-06 | Parkervision, Inc. | Apparatus and method of differential IQ frequency up-conversion |
| US8295406B1 (en) | 1999-08-04 | 2012-10-23 | Parkervision, Inc. | Universal platform module for a plurality of communication protocols |
| DE19961123A1 (en) | 1999-12-17 | 2001-07-05 | Infineon Technologies Ag | Method for estimating the frequency offset of a CPFSK signal |
| US7010286B2 (en) | 2000-04-14 | 2006-03-07 | Parkervision, Inc. | Apparatus, system, and method for down-converting and up-converting electromagnetic signals |
| US7454453B2 (en) | 2000-11-14 | 2008-11-18 | Parkervision, Inc. | Methods, systems, and computer program products for parallel correlation and applications thereof |
| JP4607391B2 (en) * | 2001-08-29 | 2011-01-05 | 株式会社日立国際電気 | Carrier wave extraction circuit |
| US7072427B2 (en) | 2001-11-09 | 2006-07-04 | Parkervision, Inc. | Method and apparatus for reducing DC offsets in a communication system |
| US7379883B2 (en) | 2002-07-18 | 2008-05-27 | Parkervision, Inc. | Networking methods and systems |
| US7460584B2 (en) | 2002-07-18 | 2008-12-02 | Parkervision, Inc. | Networking methods and systems |
Family Cites Families (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS4861063A (en) * | 1971-12-01 | 1973-08-27 | ||
| JPS55132164A (en) * | 1979-03-30 | 1980-10-14 | Nec Corp | Carrier regenerating circuit for psk demodulator |
| JPS6085650A (en) * | 1983-10-17 | 1985-05-15 | Fujitsu Ltd | Method for correcting carrier shift |
| NL8303819A (en) * | 1983-11-07 | 1985-06-03 | Philips Nv | SAMPLED COSTAS LOOP. |
-
1986
- 1986-12-08 NL NL8603110A patent/NL8603110A/en not_active Application Discontinuation
-
1987
- 1987-12-04 DK DK638687A patent/DK168843B1/en not_active IP Right Cessation
- 1987-12-04 CA CA000553505A patent/CA1273680A/en not_active Expired
- 1987-12-07 EP EP87202438A patent/EP0273504B1/en not_active Expired - Lifetime
- 1987-12-07 DE DE8787202438T patent/DE3784675T2/en not_active Expired - Fee Related
- 1987-12-07 AU AU82141/87A patent/AU8214187A/en not_active Abandoned
- 1987-12-08 US US07/130,361 patent/US4890302A/en not_active Expired - Fee Related
- 1987-12-08 JP JP62308834A patent/JP2541588B2/en not_active Expired - Lifetime
Also Published As
| Publication number | Publication date |
|---|---|
| NL8603110A (en) | 1988-07-01 |
| JP2541588B2 (en) | 1996-10-09 |
| AU8214187A (en) | 1988-06-09 |
| EP0273504A1 (en) | 1988-07-06 |
| DE3784675T2 (en) | 1993-08-26 |
| DK168843B1 (en) | 1994-06-20 |
| EP0273504B1 (en) | 1993-03-10 |
| DK638687D0 (en) | 1987-12-04 |
| JPS63160448A (en) | 1988-07-04 |
| DE3784675D1 (en) | 1993-04-15 |
| DK638687A (en) | 1988-06-09 |
| US4890302A (en) | 1989-12-26 |
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