CA1289080C - Separation of l+r from l-r in btsc system - Google Patents
Separation of l+r from l-r in btsc systemInfo
- Publication number
- CA1289080C CA1289080C CA000538392A CA538392A CA1289080C CA 1289080 C CA1289080 C CA 1289080C CA 000538392 A CA000538392 A CA 000538392A CA 538392 A CA538392 A CA 538392A CA 1289080 C CA1289080 C CA 1289080C
- Authority
- CA
- Canada
- Prior art keywords
- signal
- frequency
- component
- input
- output signal
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Fee Related
Links
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
- H04N5/00—Details of television systems
- H04N5/44—Receiver circuitry for the reception of television signals according to analogue transmission standards
- H04N5/60—Receiver circuitry for the reception of television signals according to analogue transmission standards for the sound signals
- H04N5/607—Receiver circuitry for the reception of television signals according to analogue transmission standards for the sound signals for more than one sound signal, e.g. stereo, multilanguages
Landscapes
- Engineering & Computer Science (AREA)
- Multimedia (AREA)
- Signal Processing (AREA)
- Stereo-Broadcasting Methods (AREA)
- Stereophonic System (AREA)
Abstract
Abstract of the Disclosure A stereo signal separation system for separating the L+R and L-R components of a BTSC stereo signal mixes the BTSC signal with a multiple of the pilot frequency. To recover the L+R component the mixer output is combined with the input BTSC signal, and to recover the L-R component the mixer output is combined with a second mixer output shifted ninety degrees.
The combined output is low pass filtered to recover the desired component.
The combined output is low pass filtered to recover the desired component.
Description
SEP~RATION OF L~ FROM h-R IN BTSC SYSTE~
Back~round o~ the ~n~ention The present i~ention relates to 6ignal ~eparation aircuit~, and more partiaularly to a circuit for separating the L+~ and L-~ components of stereo audio in the BTSC Bystem.
The B~SC ~ystem define~ a m~in audio L~R channel up ko 15 kHz, a pilot signal at the horizontal ~weep freguency of 15.734 k~z, and a double ~ide band, ~uppressed carrier ~tereo ~ubchannel ~ymmetrically about a frequency which ts twice the pilot 6ignal frequency. To design lowpass filter~ for this ~y~tem requires ~ilter per~ormance sç~veral order6 of magnitude beyond performance adeguats for.an FM stereo 8y5tem. ~he guaxdband~ between the main channel, the pilot signa} and the ~ubchannel ar~ much narrower, and a dbx n~i~e reduction compxes~or is placed in the subchannel, increasing th~ potential ~or subchannel to main channel crosstal~. The guardbands between the main channel and the pilot ~ignal an~ between the pilot ~ignal ~nd the subchannel are only 734 Hz each, "
'L3~
with the separation between the main channel and the subchannel being 1.468 kHZ. Thus, a significant factor in channel separation is the subchannel to main channel crosstalk.
Subchannel to main channel crosstalk occurs when the lower sideband of the subchannel leaks into the main channel due to inadequate lowpass filtering of the subchannel audio.
This crosstalk is nonlinear, i.e., it is highly offensive to the ear because it is not harmonically related to the main channel signals. Additionally when the signal levels are low but the program material contains substantial L-R content, the dbx noise reduction compressor can cause suhchannel levels to be 20-30 dB higher than main channel levels. When this occurs the main channel has negligible ability to psychoacoustically mask the crosstalk. Further the greatest gain is likaly to be produced at high frequencies -- the very frequencies that appear at the edge of the lower sideband and which are most likely to cause audible crosstalk.
High performance filters which are adequate for the BTSC
system are quite complex, one such having as many as 29 poles of filtering overall, are expensive and require great stability. If the filter is too abrupt at cutoff, the result is ringing coming out of the filter.
What is desired is a stable~ simple circuit for separating the L+R and L-R components of the BTSC signal while still eliminating crosstalk between the main channel and the subchannel.
:
Summary of the_Invention In accordance with one aspe.ct of the invention there is provided a stereo signal separation system comprising: means for mixing an input stereo signal, having a lower frequency first component, an upper frequency double sideband second component and a pilot signal at a frequency between the two components, with a multiple of the pilot signal frequency to produce a mixed output signal; means for summing said mixed output signal with said input stereo signal to produce a .
~, `' ' ~a .. summed output signal with one of said components eliminated;
and means for filtering said summed output signal to recover the remaining component.
In accordance with another aspect of the invention there is provided a stereo signal separation system comprising: a first mixing means having, as a first input, an input stereo signal, having a lower frequency first component, an upper frequency double sideband second component and a pilot signal at a frequency between the two components, and as a second input a multlple of the pilot signal frequency, and having as an output a first mixed output signal; a second mixing means having, as a first input, said input stereo signal and as a second input a phase shifted multiple of the pilot signal frequency, and having as an output a second mixed output signal; means for summing said first mixed output signal with said second mixed output signal to produce a summed output signal with one of the components eliminated; and means for filtering said summed output signal to recover the remaining component.
Accordingly the present invention provides a circuit for separatiny L+R and 1-R components of a BTSC signal by mixing the components with a given !, !;
~, i multiple of the p~lot signal ~regucncy and then adding or ~ubtra¢ting ~he resultant ~ignal~. To recover ~he L+R component the BTSC ~ignal i8 low pa6~ filtered to obtain b~th compone.nt~ ~+R ~nd L-~), the component~
5 are mixed with a s1gnal ~our ti~es the pilot s$gnal freguency, and then 6ubtracted ~r~m the unmixed, low pa~ filtered BTSC signal. ~o o~tain the L-R
component the BTSC ~ignal i~ ~ixed with an unshi~ted subcarrier freguency ~nd with a 9O degree phase shi~ted ~ubcarrier ~requency, the output o~ the 6hifted ~ixer being 6h~fted an additional 90 degraes, ~nd the DUtpUt~ 0~ the mixer~ then being Qither addad or subtracted depending upon ~he direction oP the additional phase ~hift.
The objects, advantages an~ other n~vel ~eature~
of the present invention will b~ apparent fro~ the following detailed description when read in conjunction with the appended cla~m and attached drawing.
BriQf Description of the_Drawing ~ig. 1 i8 a frequency ~omain view of a portion of the BTSC 6tereo 6ignal.
Fig. 2 ls a block diagram view o~ a circuit for obtainlng the L+~ ~omponent of the BTSC stereo signal according to the present invention.
~ig. 3 i~ a ~requ~nay domain view illustrating the operation o~ the circuit o~ Fig. 2.
Fig. 4 is a block diagram view o~ a circuit rOr obtaining the ~-R component o~ the B~SC stereo signal according to the present invention.
Fig. 5 is a frequency domain ~iew illustrating the operation of the circuit of ~ig. 4 ~L2~
Descri~tion of the Preferred Embodiment Fig. 1 illustrates a portion of ~h~ BTSC ~tereo signal hav~ng ~n ~+~ c~mponent; a double ~ideband, suppres~ed carrier L R component; and a pilot ei~nal.
The respective ~lgnal de~iation~ are 25, 50 and 5 ~' 5 kHZ. The second program channel (SAP) and the ~. . ~ ..
pro~essional channel are o~itted as not in~olved in the present invention. As is apparent ~rom this frequency domaln view any ~iltering to 6eparat~ L+R
from L-R is extremely difficult and would re~u~re a very prec~e, and hence very co~plex and expensive, ~FilterO
Referring now to Fig. 2 the B~SC ~tereo ~ignal is input to a rir~t low pass filter (LPF) lO which has a bandwidth su~icient to encompas~ both the L~R and L R
component6. The ~ilter~d out~ut from the LæF lO is input to a mixer 12 and ~ ~ummer 14. The sec~nd input to the mixer 12 $s a frequency 4~H wh$ch is ~cur times the pilGt ~re~uency fH. Sinc~ the ~-~compone~t is symmetrical about the 6uppressed carr$er frequency 2fH, i.e., the lower band i8 the mirror image of the upper band, as illustrated in Fig. 3 the difference freguencies shift the L+R component above the ~-R component while leaving the L-R componant essentially unchanged. The ~um and di~erence outputs from the ~ixer ~2 are input to the eummer 14, the dif~erence outputs being the only signi~lcant outputs. ~he summer 14 subtracts the output 3~a) ~rom the ~ixer 12 from the input 3~b) to the mixer to produce an output 3~c) which contains only the original ~R component and a frequency ~hifted L~R
component. The output ~rom the eummer 14 i6 input to a eecond low pass filter 16 to recover the original L+R component.
~2~39~0 Alternatively the L-R component may be recover~d as 6hown in Fig. 4. The BTSC stereo ~ignal is input to two mixer6 20 and 22. The 6econd input to the ~ixers 20 and 22 is the subcarrier ~reguency 2f~ in phase guadrature, i.eO, identical fre~uencies shlfted 90 degrees fr~m each other. As illustrated in Fig. 5 ~he output 5(a) of the inphase mixer 20 within the portion o~ the ~reguency domain of interest results in the L-R component being ~hifted down to below the pilot ~requency and the L+R component being shifted abo~e the pilot frequency. The output 5(b) of the phase ~hi~ted mixer 22 has only ~he L~R component 6hift d above the pilot freguency, the ~-R component having been cancelled due ko the phase shift and the ~ymmetry of the upper and lower bands. The output of the phase ~hi~ted m$xer 22 i~ passed throug~ a gO
degree phase ~hifter 24 so that the L~R component is either in phase or 180 degreeæ out o~ phase with the L~R component from the inphase mixer 20. The : 20 resulting outputs ~rom the mixerC 20 and ~2 are $nput to a summ~r 26, which either adds or 6ubtract~ the two ~ignals depending upon th0 direct~on of the 90 degree pha6e ~hi~t by the phase ~hifter 24. The re~ulting output ~(c) contains only th~ L-R component whiah can easily be obtained at this point by a low pa68 filter 28.
' Thus the present invention provide~ a circuit for ~eparating the L+R and L-R components o~ a BTSC ~tereo ~ignal by mixing the BTSC signal with a multiple o~
the pilot signal and then summing the results, reguiring only simple low pass filters in the circuit.
Back~round o~ the ~n~ention The present i~ention relates to 6ignal ~eparation aircuit~, and more partiaularly to a circuit for separating the L+~ and L-~ components of stereo audio in the BTSC Bystem.
The B~SC ~ystem define~ a m~in audio L~R channel up ko 15 kHz, a pilot signal at the horizontal ~weep freguency of 15.734 k~z, and a double ~ide band, ~uppressed carrier ~tereo ~ubchannel ~ymmetrically about a frequency which ts twice the pilot 6ignal frequency. To design lowpass filter~ for this ~y~tem requires ~ilter per~ormance sç~veral order6 of magnitude beyond performance adeguats for.an FM stereo 8y5tem. ~he guaxdband~ between the main channel, the pilot signa} and the ~ubchannel ar~ much narrower, and a dbx n~i~e reduction compxes~or is placed in the subchannel, increasing th~ potential ~or subchannel to main channel crosstal~. The guardbands between the main channel and the pilot ~ignal an~ between the pilot ~ignal ~nd the subchannel are only 734 Hz each, "
'L3~
with the separation between the main channel and the subchannel being 1.468 kHZ. Thus, a significant factor in channel separation is the subchannel to main channel crosstalk.
Subchannel to main channel crosstalk occurs when the lower sideband of the subchannel leaks into the main channel due to inadequate lowpass filtering of the subchannel audio.
This crosstalk is nonlinear, i.e., it is highly offensive to the ear because it is not harmonically related to the main channel signals. Additionally when the signal levels are low but the program material contains substantial L-R content, the dbx noise reduction compressor can cause suhchannel levels to be 20-30 dB higher than main channel levels. When this occurs the main channel has negligible ability to psychoacoustically mask the crosstalk. Further the greatest gain is likaly to be produced at high frequencies -- the very frequencies that appear at the edge of the lower sideband and which are most likely to cause audible crosstalk.
High performance filters which are adequate for the BTSC
system are quite complex, one such having as many as 29 poles of filtering overall, are expensive and require great stability. If the filter is too abrupt at cutoff, the result is ringing coming out of the filter.
What is desired is a stable~ simple circuit for separating the L+R and L-R components of the BTSC signal while still eliminating crosstalk between the main channel and the subchannel.
:
Summary of the_Invention In accordance with one aspe.ct of the invention there is provided a stereo signal separation system comprising: means for mixing an input stereo signal, having a lower frequency first component, an upper frequency double sideband second component and a pilot signal at a frequency between the two components, with a multiple of the pilot signal frequency to produce a mixed output signal; means for summing said mixed output signal with said input stereo signal to produce a .
~, `' ' ~a .. summed output signal with one of said components eliminated;
and means for filtering said summed output signal to recover the remaining component.
In accordance with another aspect of the invention there is provided a stereo signal separation system comprising: a first mixing means having, as a first input, an input stereo signal, having a lower frequency first component, an upper frequency double sideband second component and a pilot signal at a frequency between the two components, and as a second input a multlple of the pilot signal frequency, and having as an output a first mixed output signal; a second mixing means having, as a first input, said input stereo signal and as a second input a phase shifted multiple of the pilot signal frequency, and having as an output a second mixed output signal; means for summing said first mixed output signal with said second mixed output signal to produce a summed output signal with one of the components eliminated; and means for filtering said summed output signal to recover the remaining component.
Accordingly the present invention provides a circuit for separatiny L+R and 1-R components of a BTSC signal by mixing the components with a given !, !;
~, i multiple of the p~lot signal ~regucncy and then adding or ~ubtra¢ting ~he resultant ~ignal~. To recover ~he L+R component the BTSC ~ignal i8 low pa6~ filtered to obtain b~th compone.nt~ ~+R ~nd L-~), the component~
5 are mixed with a s1gnal ~our ti~es the pilot s$gnal freguency, and then 6ubtracted ~r~m the unmixed, low pa~ filtered BTSC signal. ~o o~tain the L-R
component the BTSC ~ignal i~ ~ixed with an unshi~ted subcarrier freguency ~nd with a 9O degree phase shi~ted ~ubcarrier ~requency, the output o~ the 6hifted ~ixer being 6h~fted an additional 90 degraes, ~nd the DUtpUt~ 0~ the mixer~ then being Qither addad or subtracted depending upon ~he direction oP the additional phase ~hift.
The objects, advantages an~ other n~vel ~eature~
of the present invention will b~ apparent fro~ the following detailed description when read in conjunction with the appended cla~m and attached drawing.
BriQf Description of the_Drawing ~ig. 1 i8 a frequency ~omain view of a portion of the BTSC 6tereo 6ignal.
Fig. 2 ls a block diagram view o~ a circuit for obtainlng the L+~ ~omponent of the BTSC stereo signal according to the present invention.
~ig. 3 i~ a ~requ~nay domain view illustrating the operation o~ the circuit o~ Fig. 2.
Fig. 4 is a block diagram view o~ a circuit rOr obtaining the ~-R component o~ the B~SC stereo signal according to the present invention.
Fig. 5 is a frequency domain ~iew illustrating the operation of the circuit of ~ig. 4 ~L2~
Descri~tion of the Preferred Embodiment Fig. 1 illustrates a portion of ~h~ BTSC ~tereo signal hav~ng ~n ~+~ c~mponent; a double ~ideband, suppres~ed carrier L R component; and a pilot ei~nal.
The respective ~lgnal de~iation~ are 25, 50 and 5 ~' 5 kHZ. The second program channel (SAP) and the ~. . ~ ..
pro~essional channel are o~itted as not in~olved in the present invention. As is apparent ~rom this frequency domaln view any ~iltering to 6eparat~ L+R
from L-R is extremely difficult and would re~u~re a very prec~e, and hence very co~plex and expensive, ~FilterO
Referring now to Fig. 2 the B~SC ~tereo ~ignal is input to a rir~t low pass filter (LPF) lO which has a bandwidth su~icient to encompas~ both the L~R and L R
component6. The ~ilter~d out~ut from the LæF lO is input to a mixer 12 and ~ ~ummer 14. The sec~nd input to the mixer 12 $s a frequency 4~H wh$ch is ~cur times the pilGt ~re~uency fH. Sinc~ the ~-~compone~t is symmetrical about the 6uppressed carr$er frequency 2fH, i.e., the lower band i8 the mirror image of the upper band, as illustrated in Fig. 3 the difference freguencies shift the L+R component above the ~-R component while leaving the L-R componant essentially unchanged. The ~um and di~erence outputs from the ~ixer ~2 are input to the eummer 14, the dif~erence outputs being the only signi~lcant outputs. ~he summer 14 subtracts the output 3~a) ~rom the ~ixer 12 from the input 3~b) to the mixer to produce an output 3~c) which contains only the original ~R component and a frequency ~hifted L~R
component. The output ~rom the eummer 14 i6 input to a eecond low pass filter 16 to recover the original L+R component.
~2~39~0 Alternatively the L-R component may be recover~d as 6hown in Fig. 4. The BTSC stereo ~ignal is input to two mixer6 20 and 22. The 6econd input to the ~ixers 20 and 22 is the subcarrier ~reguency 2f~ in phase guadrature, i.eO, identical fre~uencies shlfted 90 degrees fr~m each other. As illustrated in Fig. 5 ~he output 5(a) of the inphase mixer 20 within the portion o~ the ~reguency domain of interest results in the L-R component being ~hifted down to below the pilot ~requency and the L+R component being shifted abo~e the pilot frequency. The output 5(b) of the phase ~hi~ted mixer 22 has only ~he L~R component 6hift d above the pilot freguency, the ~-R component having been cancelled due ko the phase shift and the ~ymmetry of the upper and lower bands. The output of the phase ~hi~ted m$xer 22 i~ passed throug~ a gO
degree phase ~hifter 24 so that the L~R component is either in phase or 180 degreeæ out o~ phase with the L~R component from the inphase mixer 20. The : 20 resulting outputs ~rom the mixerC 20 and ~2 are $nput to a summ~r 26, which either adds or 6ubtract~ the two ~ignals depending upon th0 direct~on of the 90 degree pha6e ~hi~t by the phase ~hifter 24. The re~ulting output ~(c) contains only th~ L-R component whiah can easily be obtained at this point by a low pa68 filter 28.
' Thus the present invention provide~ a circuit for ~eparating the L+R and L-R components o~ a BTSC ~tereo ~ignal by mixing the BTSC signal with a multiple o~
the pilot signal and then summing the results, reguiring only simple low pass filters in the circuit.
Claims (5)
1. A stereo signal separation system comprising:
means for mixing an input stereo signal, having a lower frequency first component, an upper frequency double sideband second component and a pilot signal at a frequency between the two components, with a multiple of the pilot signal frequency to produce a mixed output signal;
means for summing said mixed output signal with said input stereo signal to produce a summed output signal with one of said components eliminated; and means for filtering said summed output signal to recover the remaining component.
means for mixing an input stereo signal, having a lower frequency first component, an upper frequency double sideband second component and a pilot signal at a frequency between the two components, with a multiple of the pilot signal frequency to produce a mixed output signal;
means for summing said mixed output signal with said input stereo signal to produce a summed output signal with one of said components eliminated; and means for filtering said summed output signal to recover the remaining component.
2. The stereo signal separation system of claim 1 wherein said means for mixing is comprised of a single mixer and wherein said multiple of the pilot signal frequency is four times the pilot signal frequency.
3. A stereo signal separation system comprising:
a first mixing means having, as a first input, an input stereo signal, having a lower frequency first component, an upper frequency double sideband second component and a pilot signal at a frequency between the two components, and as a second input a multiple of the pilot signal frequency, and having as an output a first mixed output signal;
a second mixing means having, as a first input, said input stereo signal and as a second input a phase shifted multiple of the pilot signal frequency, and having as an output a second mixed output signal;
means for summing said first mixed output signal with said second mixed output signal to produce a summed output signal with one of the components eliminated; and means for filtering said summed output signal to recover the remaining component.
a first mixing means having, as a first input, an input stereo signal, having a lower frequency first component, an upper frequency double sideband second component and a pilot signal at a frequency between the two components, and as a second input a multiple of the pilot signal frequency, and having as an output a first mixed output signal;
a second mixing means having, as a first input, said input stereo signal and as a second input a phase shifted multiple of the pilot signal frequency, and having as an output a second mixed output signal;
means for summing said first mixed output signal with said second mixed output signal to produce a summed output signal with one of the components eliminated; and means for filtering said summed output signal to recover the remaining component.
4. The stereo signal separation system of claim 3 further including a phase shifter means connected between the second mixing means and the summing means for shifting the phase of said second mixed output signal by ninety degrees.
5. The stereo signal separation system of claim 3 wherein said multiple of the pilot signal frequency is two times the pilot signal frequency and wherein said phase shifted multiple of the pilot signal frequency is two times the pilot signal frequency.
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| US06/882,753 US4757538A (en) | 1986-07-07 | 1986-07-07 | Separation of L+R from L-R in BTSC system |
| US882,753 | 1997-06-16 |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CA1289080C true CA1289080C (en) | 1991-09-17 |
Family
ID=25381266
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CA000538392A Expired - Fee Related CA1289080C (en) | 1986-07-07 | 1987-05-29 | Separation of l+r from l-r in btsc system |
Country Status (6)
| Country | Link |
|---|---|
| US (1) | US4757538A (en) |
| EP (1) | EP0252452B1 (en) |
| JP (1) | JPH0681109B2 (en) |
| CA (1) | CA1289080C (en) |
| DE (1) | DE3788086T2 (en) |
| DK (1) | DK345787A (en) |
Families Citing this family (32)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US4893341A (en) * | 1989-08-01 | 1990-01-09 | At&E Corporation | Digital receiver operating at sub-nyquist sampling rate |
| US5051152A (en) * | 1989-09-26 | 1991-09-24 | Air Products And Chemicals, Inc. | Preparation of urethane prepolymers having low levels of residual toluene diisocyanate |
| US5054070A (en) * | 1990-03-05 | 1991-10-01 | Qei Corporation | Stereo signal communication system and method |
| US5239585A (en) * | 1991-07-30 | 1993-08-24 | Texas Instruments Incorporated | Devices, systems, and methods for composite signal decoding |
| US7515896B1 (en) * | 1998-10-21 | 2009-04-07 | Parkervision, Inc. | Method and system for down-converting an electromagnetic signal, and transforms for same, and aperture relationships |
| US6091940A (en) | 1998-10-21 | 2000-07-18 | Parkervision, Inc. | Method and system for frequency up-conversion |
| US6694128B1 (en) | 1998-08-18 | 2004-02-17 | Parkervision, Inc. | Frequency synthesizer using universal frequency translation technology |
| US6061551A (en) | 1998-10-21 | 2000-05-09 | Parkervision, Inc. | Method and system for down-converting electromagnetic signals |
| US7236754B2 (en) | 1999-08-23 | 2007-06-26 | Parkervision, Inc. | Method and system for frequency up-conversion |
| US6813485B2 (en) | 1998-10-21 | 2004-11-02 | Parkervision, Inc. | Method and system for down-converting and up-converting an electromagnetic signal, and transforms for same |
| US7039372B1 (en) | 1998-10-21 | 2006-05-02 | Parkervision, Inc. | Method and system for frequency up-conversion with modulation embodiments |
| US6542722B1 (en) | 1998-10-21 | 2003-04-01 | Parkervision, Inc. | Method and system for frequency up-conversion with variety of transmitter configurations |
| US6370371B1 (en) | 1998-10-21 | 2002-04-09 | Parkervision, Inc. | Applications of universal frequency translation |
| US6061555A (en) | 1998-10-21 | 2000-05-09 | Parkervision, Inc. | Method and system for ensuring reception of a communications signal |
| US6049706A (en) | 1998-10-21 | 2000-04-11 | Parkervision, Inc. | Integrated frequency translation and selectivity |
| US6560301B1 (en) | 1998-10-21 | 2003-05-06 | Parkervision, Inc. | Integrated frequency translation and selectivity with a variety of filter embodiments |
| US6757659B1 (en) * | 1998-11-16 | 2004-06-29 | Victor Company Of Japan, Ltd. | Audio signal processing apparatus |
| US6704549B1 (en) | 1999-03-03 | 2004-03-09 | Parkvision, Inc. | Multi-mode, multi-band communication system |
| US6704558B1 (en) | 1999-01-22 | 2004-03-09 | Parkervision, Inc. | Image-reject down-converter and embodiments thereof, such as the family radio service |
| US6853690B1 (en) | 1999-04-16 | 2005-02-08 | Parkervision, Inc. | Method, system and apparatus for balanced frequency up-conversion of a baseband signal and 4-phase receiver and transceiver embodiments |
| US6879817B1 (en) | 1999-04-16 | 2005-04-12 | Parkervision, Inc. | DC offset, re-radiation, and I/Q solutions using universal frequency translation technology |
| US7110444B1 (en) | 1999-08-04 | 2006-09-19 | Parkervision, Inc. | Wireless local area network (WLAN) using universal frequency translation technology including multi-phase embodiments and circuit implementations |
| US7065162B1 (en) | 1999-04-16 | 2006-06-20 | Parkervision, Inc. | Method and system for down-converting an electromagnetic signal, and transforms for same |
| US7693230B2 (en) | 1999-04-16 | 2010-04-06 | Parkervision, Inc. | Apparatus and method of differential IQ frequency up-conversion |
| US8295406B1 (en) | 1999-08-04 | 2012-10-23 | Parkervision, Inc. | Universal platform module for a plurality of communication protocols |
| US7010286B2 (en) | 2000-04-14 | 2006-03-07 | Parkervision, Inc. | Apparatus, system, and method for down-converting and up-converting electromagnetic signals |
| GB2369512A (en) * | 2000-10-07 | 2002-05-29 | Motorola Inc | Signal separation of spectrally close frequencies |
| US7454453B2 (en) | 2000-11-14 | 2008-11-18 | Parkervision, Inc. | Methods, systems, and computer program products for parallel correlation and applications thereof |
| US7072427B2 (en) | 2001-11-09 | 2006-07-04 | Parkervision, Inc. | Method and apparatus for reducing DC offsets in a communication system |
| US7460584B2 (en) | 2002-07-18 | 2008-12-02 | Parkervision, Inc. | Networking methods and systems |
| US7379883B2 (en) | 2002-07-18 | 2008-05-27 | Parkervision, Inc. | Networking methods and systems |
| JP2006508571A (en) * | 2002-11-19 | 2006-03-09 | ケーブル エレクトロニクス インコーポレーテッド | Method and system for digital decoding of MTS signal |
Family Cites Families (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US4282401A (en) * | 1970-12-24 | 1981-08-04 | Sansui Electric Company | System for transmission and reception of discrete four channel stereo |
| US4497063A (en) * | 1981-06-26 | 1985-01-29 | Pioneer Electronic Corporation | FM stereo demodulator |
| US4502148A (en) * | 1981-06-26 | 1985-02-26 | Pioneer Electronic Corporation | FM Stereo demodulator for demodulating stereo signals directly from an FM intermediate frequency signal |
| JPS5943644A (en) * | 1982-09-04 | 1984-03-10 | Pioneer Electronic Corp | Fm stereo demodulating circuit |
| JPS60128732A (en) * | 1983-12-16 | 1985-07-09 | Nec Corp | Demodulator of stereo composite signal |
| JPS62219830A (en) * | 1986-03-20 | 1987-09-28 | Sony Corp | Fm stereo demodulation circuit |
-
1986
- 1986-07-07 US US06/882,753 patent/US4757538A/en not_active Expired - Lifetime
-
1987
- 1987-05-29 CA CA000538392A patent/CA1289080C/en not_active Expired - Fee Related
- 1987-06-22 JP JP62155245A patent/JPH0681109B2/en not_active Expired - Lifetime
- 1987-07-03 EP EP87109625A patent/EP0252452B1/en not_active Expired - Lifetime
- 1987-07-03 DE DE3788086T patent/DE3788086T2/en not_active Expired - Fee Related
- 1987-07-06 DK DK345787A patent/DK345787A/en not_active Application Discontinuation
Also Published As
| Publication number | Publication date |
|---|---|
| DE3788086T2 (en) | 1994-05-19 |
| DK345787A (en) | 1988-01-08 |
| EP0252452B1 (en) | 1993-11-10 |
| DE3788086D1 (en) | 1993-12-16 |
| EP0252452A2 (en) | 1988-01-13 |
| JPH0681109B2 (en) | 1994-10-12 |
| US4757538A (en) | 1988-07-12 |
| JPS6315600A (en) | 1988-01-22 |
| EP0252452A3 (en) | 1990-11-07 |
| DK345787D0 (en) | 1987-07-06 |
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Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| MKLA | Lapsed |