CN101635524A - 具有空载时间适应控制的谐振开关式功率转换器 - Google Patents
具有空载时间适应控制的谐振开关式功率转换器 Download PDFInfo
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Abstract
一种具有适应空载时间控制的谐振开关式功率转换器,能够提高效率同时降低EMI/音频噪声和器件应力。开关电路产生的脉冲之间的空载时间被设置成与谐振开关式功率转换器的输入电压的值以及流经转换器的谐振回路的电感元件的电流强度的指示相一致。电流强度的指示可以是转换器的开关频率,或者是线路或者负载电流水平的测量结果。空载时间能够从查询表中获得,或者由电流强度和输入电压值计算得到。
Description
本申请主张申请号为61/083,717,申请日为2008年7月25日的在先美国专利申请的优先权。
技术领域
本发明涉及一种开关式功率调节器电路,尤其是一种在脉冲之间的空载时间中进行适应控制的谐振开关式功率转换器。
背景技术
在谐振开关式功率转换器中,为了防止开关电路中带来的损耗和应力,非常需要在通过源极和漏极的电压差别最小的时候在开关电路中对晶体管进行切换。因为任何通过开关晶体管的现有技术和任何在晶体管激活时连接电容器的漏极-源极都会导致能量的浪费,零电压开关(ZVS)控制就非常需要。如果开关电路切换的太早,晶体管和电容器将通过开关电路被放电而浪费能量。但是,如果开关电路切换的太晚,能量将由穿过晶体管的二极管回到电源端的电流而被浪费。ZVS控制提高了电源的效率,并降低了开关晶体管承受的应力,提高了可靠性。更进一步的,开关频率产生的瞬间能够引起电磁干扰(EMI)和音频噪声,这种谐振转换器的开关频率通常会在听觉频率范围之内。
为了实现ZVS控制,脉冲之间的空载时间可以被设置成一个时间宽度,这样谐振回路的输入在一个电源附近到另一个电源之间(由于双极性脉冲)摆动,或者完成一个完整的周期(由于单极性脉冲)。但是,因为谐振转换器的频率为了控制电感器的电流以及提供给负载的能量而变化,相当于空载时间的时间宽度不会因为所有的操作条件而被校正。通常的,从由于不合适的切换时间而造成的损耗由于更高的电感器电流水平而变得更大的时候开始,空载时间习惯被设置成更高的功率操作状况(也就是,更高的频率操作状况)。
因此,提供一种能够提高效率,降低应力和音频/EMI噪声的谐振开关式功率转换器就非常有必要。
发明内容
本发明为了达到上述目的而提供了一种谐振开关式功率转换器及其操作方法,能够提高效率,降低应力,并且降低EMI和音频噪声。
谐振开关式功率转换器包括一个谐振回路,一个用来从输入电压源向谐振回路电路传输能量的开关电路,以及一个将谐振回路电路耦合至开关式功率转换器的输出的变压器。开关电路产生的脉冲之间的空载时间被一个控制电路适应性的设置,从而与输入的电压和流过谐振回路电路的电感元件的电感器电流相一致。
电感器电流可以由开关频率,流过电感元件电流的直接或者间接的计量,或者另外的相关数值,例如电源的输出负载电流或者输入线路电流来衡量。控制电路可以由电流指示一个周期一个周期的计算空载时间,或者使用一个查询表,其中的空载时间设置与输入电压和电感器电流值相一致。
本发明的上述及其它目的、性能和进步将在下文结合实施例与图示进行详细的说明。
附图说明
图1为本发明谐振开关式功率转换器一个实施例的原理图;
图2A和图2B为本发明图1所示实施例中作为开关控制电路10使用的空载时间控制电路的模块图;
图3为图1所示的开关式功率转换器的工作时序图;
具体实施方式
本发明提供的电路和方法,在谐振开关式功率转换器中的脉冲之间适应性的控制空载时间,以提高转换器的效率,并且降低应力和音频/EMI噪声。空载时间被控制与转换器的输入电压及流过谐振开关式功率转换器电路所采用的谐振回路中的电感的电流强度相一致。
图1所示为本发明一个实施例的谐振开关式功率转换电路。一个开关控制电路10控制由晶体管N1和N2组成的开关电路。一个由电感和电容构成的串联的谐振回路电路由晶体管N1和N2的开关动作来提供能量。一个变压器T1将能量从谐振回路电路耦合至一个为输出电容C3充电提供整流电流的整流电桥BR1。输出电压VOUT可以在向开关控制电路10提供反馈信号的反馈电路12的操作中被保持在一个预先设定的电压上。作为选择的,关于输出电压VOUT的操作可以式开环的,这是针对输出的负载阻抗没有预期的充分变化的情况而进行的特殊的适应性设计。开关控制电路10可以是集成在一个单晶片上的集成电路,也可以包括图1中所示电路的其它元件,例如,开关晶体管N1和N2和/或反馈电路12。
在图1中,谐振回路电路的电感,如图所示,包括电感器L1加上变压器T1初级线圈的任何漏电感。但是,谐振回路电路的电感也可以完全由变压器的漏电感提供,因此电感器L1在本发明的一些实施例中是不存在的。谐振回路电路的电容由回路中串联的总电容提供,如图所示,包括并联的电容器C1和C2,与变压器T1初级线圈处的整流电容并联的寄生线圈电容CT,以及当晶体管N1和N2都不导通时,晶体管N1和N2的并联连接的寄生电容(CpN1和CpN2)。
开关控制电路10适应性的控制由于晶体管N1和N2切换而产生的脉冲之间的空载时间,晶体管N1和N2交替导通,以提供极性相反的交替脉冲,这由连接到电感器L1和电容器C1-C2构成的谐振回路电路的相应的电源电压+VIN或者-VIN提供。如果脉冲之间没有空载时间,当晶体管N1和N2中的一个导通,寄生电容CpN1和CpN2中的相应的一个上面的电荷将被放电。相似的,寄生电容CpN1和CpN2中的另外一个也将突然加载到几乎满载的输入电压上。当没有空载时间的时候对寄生电容CpN1和CpN2充电和放电的电荷浪费了能量,并且降低了谐振转换器的效率。更进一步的,对寄生电容CpN1和CpN2充电和放电的更高的电流水平提高了晶体管N1和N2中的应力水平,并且能够引起EMI和/或音频噪声。通过提供空载时间,这样在一个脉冲结束之后,当下一个脉冲发生并且使得晶体管N1或者N2中的一个导通时,电压VS在相反的电源端电压附近摆动,相应的寄生电容放电的电压将将会小的多,并且提高了谐振功率转换器的效率。这样的操作通常被称为零电压切换(ZVS),如上所述,由于频率越高损耗就越大,(每个单元时间间隔产生更多的瞬间,因此造成更多的能量浪费),空载时间通常被设置成在谐振开关式功率转换器的操作的最高频率附近提供ZVS操作。
在本发明中,脉冲中的空载时间被适应性的控制。尤其是,在本发明一个实施例的谐振功率转换器的数字部件中,脉冲的时间由计数器决定,并且提供的任何空载时间也都根据一个计数值产生,并且被设置与输入电压的数值和流过电感器L1的电感器电流强度相一致,从而保持一个适当的空载时间以提供ZVS操作,或者作为选择的,操作中导通的晶体管的寄生电容上仍然存在的电压从全功率电源电压的范围被充分降低。
电感器电流IL的强度的指示可以从很多方面获得,包括直接测量电感器电流的测量电路,例如实施例中所描述的由电感器CS和电阻RS提供。因为在连接变压器T2到电容器CS的节点的返回电流在电容器C1,C2和CS之间被分流,如果电容CS的电容值相对较小,一小部分电感电流IL将流过电容器CS并且产生一个与穿过电阻器RS的电感器电流IL成比例的电压压降。经过电阻器RS的的电压之后能够被用作电感器电流的直接指示αIL,而不会对谐振开关式功率转换器的效能产生明显的影响。电阻器RS能够作为包含有开关控制电路10的集成电路的一部分,并且从内部连接电源电压-VIN。在这个实施例中,电容器CS被连接到集成电路的一个管脚,从而直接接收穿过电容器CS的电感电流IL的一部分,并且作为电感器电流IL的指示。
作为附加的,或者作为选择的,上述电感器电流的测量,电感器电流IL的强度指示可以是谐振转换器的操作频率,因为电感器电流IL通常与操作的频率成比例。对于数字控制转换器,由于一个分频器或者其它装置被用来产生生成控制晶体管N1和N2栅极端的控制信号CA和CB的开关频率,操作频率通常已经在开关控制电路10中的一些数字中被精确设定。并且,在电流模式的谐振转换器中,输出电流强度的指示从反馈电路12中被提供,同时被用来控制谐振开关式功率转换器的开关频率,并且因此也与电感器电流IL成比例。在电压模式的谐振转换器中,一个电流的负载电流感应电路可以被包括,用来提供电感器电流强度的指示,并且还可以用作其它目的,例如过流保护。最后,电感器电流能够被串联感应电阻器,或者一个第二电感器线圈感应到,第二电感器线圈被提供给一个包含有穿过电感器线圈电压的电路,例如一个模拟低通滤波器。
因为操作频率根据线路和负载情况进行调整以保持一个特定的输出电压或电流水平,线电压也在开关控制电路10中以一些形式产生。因此,使用开关控制电路中可用的频率和电压信息,空载时间能够被设置成不同的值,以在图1所示的谐振开关式功率转换器中的整个频率及负载/线路状况范围内提供ZVS操作。
图2A所示为本发明的一个实施例中可以应用于图1中的开关控制电路10的适应性空载时间控制电路。一个计算模块20A接收至少一个输入电压值VI和一些流过电感器L1的电流强度的指示,这可以是开关频率FS,测量得到的电感器电流αIL,或者两者皆有。计算模块20A根据输入值计算出一个输出值Dead Time Count,这个输出值之后被用来设置一个决定前一个脉冲的结束边沿和后一个脉冲的开始变压之间的时间的空载时间计数器22。计算模块20A可以是一个根据输入电压值VI和表示电感器电流指示的频率FS和/或电感器电流αIL计算输出值Dead Time Count的处理器元件,或者可以采用一个专用的数字电路作为计算模块20A。
图2B所示为本发明另一个实施例中可以应用于图1所示的开关控制电路10的适应性空载时间控制电路。一个查询表20B按规则记录有至少一个输入电压值VI和一些流过电感器L1的电流强度指示,这个指示可以是开关频率FS,测量得到的电感器电流αIL,或者两者皆有。查询表20B根据输入值的选择提供一个之后被用来设置空载时间计数器22的输出值Dead TimeCount。
图3所示为图1所示的谐振开关式功率转换器的操作。在控制信号CA和CB激活状态(高电平)之间,提供一个可变化的空载时间td,以根据设定与输入电压VI和电感器电流强度的指示一致。电压VS在空载时间中变化到电压VZL或者电压VZH,是依据电感器电流IL的极性。(当没有开关晶体管导通的时候,电感器电流IL使电容通过之前对电感器充电的晶体管放电,这可以从空载时间中电感器电流IL的变化趋势看出来)。如图中很清晰的表示,电压VZL或者电压VZH从电源中分出来,并且如图所示,其大约为电源的25%,这能够使得相对于寄生电容CpN1和CpN2充电和放电中浪费的能量,效率提高的比率大约是16∶1。但是,空载时间最后的电压能够被精确的设置成与下一个应用于谐振回路的电源不同的零电压,使得寄生电容CpN1和CpN2的放电根本不会发生。更进一步的,因为电压VS不会在空载时间中超过电源,但是同时会由于谐振回路振荡的开始而反向,空载时间能够被控制电路设置到由于振荡的开始而发生的电压VS反向的附近,既可以是之前,也可以是之后的任意一点。
本文对本发明做了特殊说明并参照其优选实施例进行了描述,熟悉本领域的技术人员能够领会本发明,并可以在不超出本发明的构思与范围的前提下对上述实施例的细节做出其它形式的变更。
Claims (20)
1.一种谐振开关式功率电路,包括:
一个谐振电路,包括至少一个电感和至少一个电容,用来向谐振开关式功率电路的输出传输能量;
一个开关电路,耦合至谐振电路,用来从一个输入电压源向谐振电路传输能量,其中开关电路包括一个第一晶体管,用来选择性的将谐振电路耦合到输入电压源的输出节点,以及一个第二晶体管,用来选择性的将谐振电路耦合至输入电压源的一个返回节点;以及
一个控制电路,用来控制开关电路,使得一个空载时间,在第一晶体管或者第二晶体管中的一个被截止和第二晶体管或者第一晶体管中的第二个被导通之间,被动态的根据流过电感的电流强度的指示和输入电压源的电压而设定。
2.根据权利要求1所述的谐振开关式功率电路,其中流过电感的电流强度的指示是开关电路工作时候的开关频率。
3.根据权利要求1所述的谐振开关式功率电路,还包括一个电流测量电路,用来测量流过电感的电流,并且其中流过电感的电流强度的指示从电流测量电路测输出中得到。
4.根据权利要求3所述的谐振开关式功率电路,其中电流测量电路包括:
一个感应电容器,并联耦合至谐振回路电路的电容;以及
一个感应电阻器,串联耦合感应电容器,使得感应电阻器的电压压降提供电感器电流强度的指示。
5.根据权利要求1所述的谐振开关式功率电路,其中流过电感的电流强度指示是测量得到的谐振开关式功率电路输出的负载电流。
6.根据权利要求1所述的谐振开关式功率电路,其中控制电路包括一个查询表,从中空载时间值根据流经电感的电流强度的指示和输入电压源的电压值而被提取,并且其中控制电路控制第一和第二晶体管的开关时间与空载时间值一致。
7.根据权利要求1所述的谐振开关式功率电路,其中控制电路包括一个根据流过电感的电流强度的指示和输入电压源的电压值计算空载时间值的电路,并且其中控制电路控制第一和第二晶体管的开关时间与空载时间值相一致。
8.一种在谐振开关式功率电路中控制开关的方法,所述方法包括:
从一个谐振回路电路向谐振开关式功率电路的输出传输能量;
从一个输入电压源由开关电路的操作向谐振电路传输能量;以及
控制开关电路脉冲之间的空载时间与输入电压源的电压和流经谐振回路电路的电感的电流强度的指示一致。
9.根据权利要求8所述的方法,其中流经电感的电流强度的指示是开关电路操作中的开关频率。
10.根据权利要求8所述的方法,还包括测量流经电感的电流,并且其中流经电感的电流强度的指示从测量结果中得到。
11.根据权利要求10所述的方法,其中所述测量包括:
使得流经谐振回路电路的电容的部分电流流过一个感应电容器;以及
测量串联耦合至感应电容器的感应电阻器的电压压降,以提供电感器电流强度的指示。
12.根据权利要求8所述的方法,还包括测量谐振开关式功率电路输出的负载电流的值,其中流经电感的电流强度的指示由负载电流值决定。
13.根据权利要求8所述的方法,其中控制空载时间包括根据流经电感的电流强度的指示和输入电压源的电压值从查询表中提取空载时间值,并且其中控制设置使脉冲之间的空载时间与空载时间值相一致。
14.根据权利要求8所述的方法,还包括根据流经电感的电流强度的指示和输入电压源的电压值计算空载时间值,并且其中控制设置使脉冲之间的空载时间与空载时间值相一致。
15.一个集成电路控制器,集成在一个单晶片上,用来控制谐振开关式功率转换器,其中集成电路控制器为一个开关电路提供控制信号而产生脉冲,提供给从输入电压源向负载传输功率的谐振回路电路的输入,并且其中控制器包括一个控制电路,用来控制脉冲之间的空载时间与输入电压源的电压值和流经谐振回路电路的电感的电流强度的指示一致。
16.根据权利要求15所述的集成电路控制器,其中流经电感的电流强度的指示是开关电路工作的开关频率。
17.根据权利要求15所述的集成电路控制器,还包括用来接收流经电感的电流指示的电压或电流的输入,并且其中流经电感的电流强度的指示从该输入中获得。
18.根据权利要求15所述的集成电路控制器,还包括用来接收提供给负载的负载电流的指示的电压或电流的输入,并且其中流经电感的电流强度的指示从该输入中获得。
19.根据权利要求15所述的集成电路控制器,其中控制电路包括一个查询表,从中可以根据流经电感的电流强度的指示和输入电压源的电压值提取空载时间,并且其中控制电路控制第一和第二晶体管的开关时间与空载时间相一致。
20.根据权利要求15所述的集成电路控制器,其中控制电路包括根据流经电感的电流强度的指示和输入电压源的电压值计算空载时间值的电路,并且其中控制电路控制第一和第二晶体管的开关时间与空载时间值相一致。
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- 2009-07-16 WO PCT/US2009/050831 patent/WO2010011559A1/en active Application Filing
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- 2009-07-20 TW TW098124455A patent/TWI452817B/zh active
- 2009-07-20 TW TW98124453A patent/TWI469487B/zh active
- 2009-07-21 TW TW98124553A patent/TWI473126B/zh active
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CN104535818A (zh) * | 2010-09-22 | 2015-04-22 | 英飞凌科技股份有限公司 | 用于di/dt电流感测的方法及装置 |
DE102011122855B4 (de) | 2010-09-22 | 2022-06-02 | Infineon Technologies Ag | Verfahren und Vorrichtung zum Messen von Stromgradienten |
CN102005927A (zh) * | 2010-11-30 | 2011-04-06 | 中国工程物理研究院流体物理研究所 | 用查表法修正串联谐振开关变换器谐振漂移的装置及方法 |
CN103460584A (zh) * | 2011-01-19 | 2013-12-18 | Abb有限公司 | 谐振功率转换器 |
CN108631598A (zh) * | 2011-01-19 | 2018-10-09 | Abb有限公司 | 谐振功率转换器 |
CN104300798A (zh) * | 2013-07-17 | 2015-01-21 | 富士电机株式会社 | 开关电源的控制装置 |
TWI672899B (zh) * | 2018-02-09 | 2019-09-21 | 大陸商明緯(廣州)電子有限公司 | 諧振轉換器的控制方法 |
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WO2010011559A1 (en) | 2010-01-28 |
CN101635512A (zh) | 2010-01-27 |
TW201106603A (en) | 2011-02-16 |
CN101635524B (zh) | 2014-02-19 |
CN101635512B (zh) | 2014-03-12 |
US8279628B2 (en) | 2012-10-02 |
EP2313965A4 (en) | 2015-11-04 |
TWI465026B (zh) | 2014-12-11 |
US20100020573A1 (en) | 2010-01-28 |
TWI456206B (zh) | 2014-10-11 |
CN102165679B (zh) | 2014-07-02 |
US20100020570A1 (en) | 2010-01-28 |
CN101707121A (zh) | 2010-05-12 |
US20100019874A1 (en) | 2010-01-28 |
US8847719B2 (en) | 2014-09-30 |
US8553430B2 (en) | 2013-10-08 |
TW201012040A (en) | 2010-03-16 |
US8330434B2 (en) | 2012-12-11 |
EP2313965A1 (en) | 2011-04-27 |
US8014176B2 (en) | 2011-09-06 |
TW201009858A (en) | 2010-03-01 |
CN101707121B (zh) | 2013-05-08 |
TWI469487B (zh) | 2015-01-11 |
TWI452817B (zh) | 2014-09-11 |
EP2313965B1 (en) | 2017-01-18 |
US20100020579A1 (en) | 2010-01-28 |
US20100020569A1 (en) | 2010-01-28 |
TW201009358A (en) | 2010-03-01 |
CN101651424A (zh) | 2010-02-17 |
CN101651424B (zh) | 2014-03-12 |
CN102165679A (zh) | 2011-08-24 |
TWI473126B (zh) | 2015-02-11 |
TW201014137A (en) | 2010-04-01 |
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