CN101651424A - 具有触发模式过渡成形的谐振开关式功率转换器 - Google Patents
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Abstract
一种具有触发模式过渡的谐振开关式功率转换器,在低负载或者零负载的情况下降低音频噪声和器件应力,同时提高效率。产生的脉冲触发中在开始和/或结束脉冲的与触发中脉冲的脉宽不同,从而降低触发开始和/或结束瞬间的振幅。更进一步的,触发开始和/或结束时的脉冲的间隔也与触发中部脉冲的间隔不同,从而减小所述瞬间。在触发开始和/或结束的时候大量的脉冲也可以被设置成具有逐渐变化的脉宽,从而更进一步的减小将谐振回路耦合至转换器的输出的变压器中的器件应力和音频震动。
Description
技术领域
本发明涉及一种开关式功率调节电路,尤其是一种谐振开关式功率转换器,其中在触发开始及结束的脉冲宽度会被减小。
背景技术
在谐振开关式功率转换器中,当输出电流需求降低,开关频率就升高以减小功率输出。但是,当遇到低负载或者零负载的情况时,所需要的开关频率可能会变得失效,并且通常会由于开关损耗的增加及输出功率对比正常开关操作下的功率消耗的下降而产生效率突然下降。由于上述原因,低功率“触发”模式就被应用到很低的或者零输出电流需求时候,此时由于发出了一个触发脉冲来重新启动谐振电路达到一个足够的水平以对谐振开关功率转换器的输出电容充电,使得输出电压能够被保持住。在触发与触发之间,输出电容为负载提供功率。
但是,通常触发动作会对谐振开关式功率转换器的部件产生应力,尤其是,开关晶体管在触发开始和触发结束的时候会提供更高的瞬间电流。电路中的变压器和/或电感器也会受到机械应力的作用,从而造成音频噪音,并可能对变压器造成累积的机械损坏。最后,在通常的触发动作中产生的功率明显会在上述不希望产生的机械震动中被浪费,例如以热的形式。
因此,现在非常需要有一种具有低功率操作模式的谐振开关式功率转换器,能够减小音频震动,减小对器件的应力并且提高效率。
发明内容
本发明提供了一种谐振开关式功率转换器及其操作方法,以达到上述为谐振开关式功率转换器提供低功率操作模式的目的,具有减小音频震动,减小器件应力以及改善效率的效果。
本发明谐振开关式功率转换器包括一个谐振回路电路,一个由输入电压源为所述谐振回路电路传输能量的开关电路,以及一个将所述谐振回路电路耦合至所述开关式功率转换器的输出端的变压器。在低功率操作模式下,所述开关电路产生具有不同脉宽和/或间隔的触发脉冲以减小开始和/或结束时刻由触发引起的振幅。触发的最后一个脉冲可以具有比触发中部的脉冲更短的脉宽,这最后一个脉冲在距离感应电流变为零的那一刻足够近的位置终结所述触发。触发的第一个脉冲也可以具有短脉宽,以避免超过触发开始时候的振幅。更进一步的,触发中在最初的和/或最后的脉冲的间隔可以与触发中部的脉冲间隔不同以降低瞬间损耗。
触发开始时和结束时的大量脉冲的脉宽可以预先设置成在触发开始的时候逐渐增加,在触发结束的时候逐渐减少,从而进一步减小由于谐振操作开始和停止而引起的瞬时电流、应力和音频震动。在触发结束时留在开关电路输出的电压与下一个触发开始时的脉冲极性相反,从而减小触发的第一个脉冲开始时开关电路输出产生的电压阶跃的幅度。开关电路可以更进一步使触发总是包含完整的半周期的偶数总和,从而避免每个触发与触发间隔的不对称。
以下将结合附图及实施例,对本发明中上文已经描述的以及其它目的、特征以及先进之处进行更详细的描述。
附图说明
图1为本发明谐振开关式功率转换器一个实施例的原理示意图;
图2为图1所示的开关式功率转换器的触发模式的时序图;
图3为图2所示的时序中触发的详细时序图;
图4为本发明采用图1所示的开关式功率转换器实现的另一个实施例的触发的时序图;
图5为本发明采用图1所示的开关式功率转换器实现的又一个实施例的触发的时序图。
具体实施方式
本发明包括了在工作于低功率触发模式下的谐振开关式功率转换器的输出变压器减小器件应力和音频震动的电路和方法。由于减小了开始和停止瞬间浪费的能量,低功率触发模式中的效率也被提高了。
图1所示为本发明谐振开关式功率转换器电路的一个实施例。一个开关控制电路10由晶体管N1和N2控制开关电路。由一个电感和一个电容构成的串联谐振回路电路由晶体管N1和N2的开关动作来提供能量。一个变压器T1将能量从谐振回路电路耦合至一个整流电桥BR1,来提供整流后的电流为输出电容C3充电。输出电压VOUT可以由为开关控制电路10提供反馈信号的反馈电路12在触发模式中保持在一个预先设定的电压上。作为选择的,触发模式也可以是“自由转动(free-wheeling)”,这样那个足以为触发模式操作提供足够低的负载电流的触发,可以提前被设定并且不需要由反馈控制来提供。
在图1中,谐振回路电路的电感可以采用如电感器L1加上变压器T1初级线圈的任意漏电感。然而,谐振回路电路中的电感也可以完全由变压器T1的漏电感来提供,因此在本发明的一些实施例中就没有电感器L1。谐振回路电路的电容由回路中串联连接的电容来提供,例如包括并联连接的电容C1和C2,在变压器T1初级线圈并联任何反射电容的寄生线圈电容CT,以及当晶体管N1和N2都截止时,晶体管N1和N2并联连接的寄生电容(CpN1和CpN2)。
在低负载或者开路情况下,开关控制电路10工作在触发模式下,以保持谐振开关式功率转换器电路在这种状况下的效率。因为由开关控制电路10产生的开关频率一般会非常高并且随负载电流的减小由串联谐振回路电路的谐振频率而升高,对晶体管N1和N2进行开关操作带来的损耗一般也会很高并且随负载的降低而增加。因此,为了使输出电压VOUT保持在期望的水平,最好的方法就是探测输出电压VOUT的下降,并且由开关控制电路10产生一个脉冲的触发,从而为谐振回路提供能量,使得对输出电容C3充电,同时保证触发之间的时间足够长。更进一步的,如上所述,触发可以根据输出电压VOUT传输给负载的最小电流所需要的最小触发长短和触发间隔,对产生的触发进行预先的设定。
图2所示为图1所示的谐振开关式功率转换器电路触发模式操作的实施例的一个时序图。在时刻T1,一个触发开始并且包括六个正脉冲和六个负脉冲。控制信号CA控制晶体管N1产生电压达到VS的正脉冲,并且由开关电路(例如图1中的晶体管N1和N2)提供给谐振回路电路。控制信号CB控制晶体管N2产生电压达到VS的负脉冲。在本发明中,脉冲的宽度不是都完全一样的。例如,触发的第一个和最后一个脉冲的脉宽被减去了其它脉冲宽度的一半,这在下文将会进行详细的描述。在时刻T2,第一个触发结束并且电压VS不再由晶体管N1和N2加载到输入电压的水平,而由谐振回路电路的“振荡(ringing)”来产生。
如图3所示为本发明谐振开关式功率转换器触发模式操作下更进一步的实施例。如上所述,在时刻Ta和Tb之间,一个半个脉宽的正脉冲由控制信号CA的动作在电压VS中产生。穿过电感器L1的电感电流IL(或者穿过其它为谐振回路电路提供串联电感的电感部件的电流)在时刻Tb升高至峰值。随后,由控制信号CB的动作而产生的负脉冲,和由控制信号CA的动作而产生的正脉冲,继续在电感电流IL中产生大小相等,极性相反的峰值,并且具有一个“完整脉宽(full duration)”,即是开始的半脉宽脉冲的两倍,例如时刻Tc和Td之间的脉宽。如果触发的第一个脉冲的脉宽也是完整的(也就是具有和触发中部的脉冲的脉宽相同),电感电流IL的第一个峰值就会有图中所示的峰值的两倍,从而产生一个瞬间,在开关晶体管N1和N2,以及变压器T1和其它与变压器T1的初级线圈串联的器件中引起应力,并由于磁感应(magneto-restriction)在变压器T1和电感器L1中引起音频噪声。由于使得输出电容的充电电流IOC具有更高的峰值,所造成的瞬间也会更快的对输出电容器C3充电,这将增加电容器C3和整流电桥BR1的应力。
采用半脉宽的脉冲作为起始,而不是完整脉宽脉冲,每个触发开始时候的瞬间电流就会被消除。进一步来说,在每个触发的结束时候,相反极性的(实施例中是负脉冲)半脉宽的脉冲在时刻Te和Tf之间产生,以防止在触发结束时产生类似的瞬间。在时刻Tg时,谐振回路的振荡如图所示,在电感器电流IL和电压VS之间具有90度的相位差。必须有偶数个正负脉冲(例如,5个完整脉宽的正脉冲和负脉冲,一个半脉宽的正脉冲和一个半脉宽的负脉冲)使触发中电感器电流IL保持在平均值为零,这样每个触发的开始时刻的零电感器电流保证结束时刻的电感器电流也为零。上述动作确保电感电流IL完全不会在触发开始和结束的时候因晶体管N1和N2的导通与断开而断开,从而进一步降低瞬间的应力和声音的影响。
图4所示为本发明如图1所示的谐振开关电路的触发模式另一个实施例。图4中的触发模式的实施例与图2和图3所示的触发模式的实施例相似,因此以下只对他们的不同之处进行描述。在图4所示的触发模式中,触发开始和结束的被缩短的脉冲不仅仅是一个,两个或者更多的脉冲相比于触发中部的脉冲的脉宽(时刻Td-时刻Tc)被缩短。缩短两个或者更多的脉冲会有两个好处:1)触发开始和结束时候的瞬间特性被更进一步的缓解;2)效率被更进一步的提高并且开关瞬间会由于为产生下一个触发脉冲而开关的谐振回路电路的“振荡(ringing)”结束时的静态值VS的改变而减小。为完成第二个脉冲,触发的第一个脉冲(和最后一个脉冲)的极性是交替的,如图中所示,这可以通过图示中在每个触发之间交换控制信号CA和CB的波形来实现。
在时刻Tb和时刻Tb’中触发的一个第二脉冲产生,其脉宽与触发开始时候的半脉宽脉冲以及触发中部完整脉宽的脉冲都不同(例如,3/4脉宽),类似的情况也出现在时刻Te’和时刻Te中,一个极性相反的相同脉宽脉冲使得电感器电流IL的最终平均值为零。但是,尽管电感器电流IL保持在总体为零的水品,触发之间的电压VS仍不能保持在总体为零的水平。在第一个触发结束的时刻Tf,一个偏置电压-Voff仍然保持在开关电路的输出(例如,图1中共同连接端上晶体管N1和N2的寄生电容CpN1和CpN2)。通过触发中交替的极性(通过交换控制信号CA和CB的控制波形),下一个触发开始时刻Ta’的极性与上一个触发结束的脉冲极性相同,并且开关电路产生的电压变化因为偏置电压Voff的值而减小,从而减小开关晶体管N1和N2的应力以及线路瞬时电脉冲。在第二个脉冲结束的时刻Tf’,电压+Voff仍然保持为VS的静态值,以配合在下一个触发开始时产生的正脉冲的极性。
图5所示为本发明图1所示的谐振开关式电路的另一个实施例的触发模式。图5所示的触发模式与图3和图4所示的触发模式相似,因此以下只对它们之间的不同之处进行描述。在图5所示的触发模式中,没有在触发结束时缩短两个脉冲,而在每个触发结束时的电压VS中设置一个偏置电压,触发结束时脉冲之间的时间是可以变化的。一个如图3所示的实施例中的半脉宽脉冲在触发结束的时候产生,但是触发的最后一个脉冲延迟了一个时间间隔Tdelay。通过改变电感器电流IL归零的时间,电压VS的值在零电感器电流的时刻被改变,这引起了偏置电压+Voff以在开关电路的输出保持类似于图4所示的情况。通过变化Tdelay的值,偏置电压+Voff的值和极性能够被控制。在图示的实施例中,每个周期结束时在电压VS的静态值中产生正极的偏置电压+Voff,图中所示为偏置电压产生以及随触发最后一个脉冲的变化而调整的方式,以及为了通过与保持在开关电路输出的电压极性相匹配的脉冲极性启动下一个触发的开关动作,起始脉冲的极性在相同数值下保持的方式(例如,开关控制信号CA和CB的波形在触发之间没有交换)。无论如何,通过进一步延迟触发最后的脉冲和/或改变触发中其它脉冲的时间,如此交替的动作以及每个周期结束时电压VS的静态值进一步的“调整(tuning)”就可以实现。
本文对本发明做了特殊说明并参照其优选实施例进行了描述,熟悉本领域的技术人员能够领会本发明,并可以在不超出本发明的构思与范围的前提下对上述实施例的细节做出其它形式的变更。
Claims (27)
1.一种谐振开关式功率电路,包括:
一个谐振电路,包括将能量传送至谐振开关式功率电路的输出的至少一个电感和至少一个电容;
一个开关电路,耦合至谐振电路将能量从电压源输入端传送到谐振电路;以及
一个控制电路,控制开关电路,其中控制电路具有一个触发模式操作,在该模式下大量的脉冲在触发中产生,在谐振开关式功率电路输出的能量需求很低的时候用来为谐振开关式功率电路的输出间歇的提供能量,并且触发中的脉冲的波形不是均一的,在触发的开始或结束时至少有一个瞬间的振幅被降低。
2.根据权利要求1所述的谐振开关式功率电路,其中触发结束脉冲中至少一个的脉宽被预先设定,与触发中部其它脉冲预先设定的脉宽不同。
3.根据权利要求1所述的谐振开关式功率电路,其中触发开始脉冲中至少一个的脉宽预先设定,与触发中部其它脉冲预先设定的脉宽不同。
4.根据权利要求1所述的谐振开关式功率电路,其中触发最初的两个脉冲之间的时间间隔与触发中另外两个脉冲之间的时间间隔不同。
5.根据权利要求1所述的谐振开关式功率电路,其中触发中至少一个结束脉冲是单脉冲。
6.根据权利要求5所述的谐振开关式功率电路,其中触发中至少一个结束脉冲的预先设定的脉宽等于触发中部另一个预先设定的脉宽的一半。
7.根据权利要求1所述的谐振开关式功率电路,其中触发中至少一个结束脉冲包括至少两个脉冲。
8.根据权利要求7所述的谐振开关式功率电路,其中触发的一个第一脉冲的极性在触发与触发之间改变。
9.根据权利要求8所述的谐振开关式功率电路,其中至少两个脉冲所具有的脉宽,使得一个非零的电压偏置在至少两个脉冲都结束之后出现在开关电路的输出上,其中触发的第一个脉冲与非零的电压偏置具有相同的极性,借此,开关电路输出的电压阶跃的幅度由于触发第一个脉冲而降低。
10.根据权利要求1所述的谐振开关式功率电路,其中触发的一个第一脉冲的极性在触发与触发之间被改变。
11.根据权利要求1所述的谐振开关式功率电路,其中每个触发的脉冲数量为偶数。
12.根据权利要求1所述的谐振开关式功率电路,其中触发的至少一个结束脉冲的开始时刻被延迟,一个非零的电压偏置在至少一个的结束脉冲终结之后出现在开关电路的输出上,其中触发的第一个脉冲的极性与触发的第一个脉冲开始时开关电路输出的偏置电压的极性相同,借此,开关电路输出的电压阶跃的幅度由于触发第一个脉冲而降低。
13.一种谐振开关式功率电路在低功率触发模式操作中的降低瞬时振幅的方法,所述方法包括:
从谐振回路电路向谐振开关式功率电路的输出传输能量;
由开关电路的动作从一个输入电压源向谐振电路传输能量;以及
在触发模式下操作开关电路,在触发中产生大量的脉冲在谐振开关式功率电路输出的能量要求很低的时候间隔的为谐振开关式功率电路的输出提供能量,并且其中触发中的脉冲具有不均一的波形,触发开始或者结束时的至少一个瞬间的振幅被降低。
14.根据权利要求13所述的方法,其中触发的至少一个结束脉冲的预先设定的脉宽与触发中部的另一个预先设定的脉宽不同。
15.根据权利要求13所述的方法,其中触发的至少一个开始脉冲的预先设定的脉宽与触发中部的另一个预先设定的脉宽不同。
16.根据权利要求13所述的方法,其中触发最初的两个脉冲之间的时间间隔与触发中另外两个脉冲之间的时间间隔不同。
17.根据权利要求13所述的方法,其中触发的至少一个结束脉冲是一个单脉冲。
18.根据权利要求17所述的方法,其中触发的至少一个结束脉冲的预先设定的脉宽等于触发中部另一个预先设定的脉宽的一半。
19.根据权利要求13所述的方法,其中触发的至少一个结束脉冲包括至少两个脉冲。
20.根据权利要求19所述的方法,其中触发的一个第一脉冲的极性在触发与触发之间被改变。
21.根据权利要求20所述的方法,其中至少两个脉冲所具有的脉宽,使得一个非零的电压偏置在至少两个脉冲都结束之后出现在开关电路的输出上,其中触发的第一个脉冲与非零的电压偏置具有相同的极性,借此,开关电路输出的电压阶跃的幅度由于触发第一个脉冲而降低。
22.根据权利要求13所述的方法,其中触发的一个第一脉冲的极性在触发与触发之间被改变。
23.根据权利要求13所述的方法,其中每个触发中的脉冲数量为偶数。
24.根据权利要求13所述的方法,其中触发的至少一个结束脉冲的开始时刻被延迟,一个非零的电压偏置在至少一个的结束脉冲终结之后出现在开关电路的输出上,其中触发的第一个脉冲的极性与触发的第一个脉冲开始时开关电路输出的偏置电压的极性相同,借此,开关电路输出的电压阶跃的幅度由于触发第一个脉冲而降低。
25.一个集成电路控制器,集成在一个单晶片上,用来控制一个谐振开关式功率转换器,其中集成电路控制器向一个具有低功率触发模式的开关电路提供控制信号,当谐振开关式功率转换器输出的能量需求很低的时候,在触发中产生大量的脉冲,并且其中触发中的脉冲具有不均一的波形,触发开始或者结束时至少一个瞬间的振幅被减小。
26.根据权利要求25所述的集成电路控制器,其中触发的至少一个开始或者结束脉冲具有另外一个与触发中部脉冲宽度不同的预先设定的脉宽。
27.根据权利要求26所述的集成电路控制器,其中开关电路集成在这个晶片上。
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US20100020569A1 (en) | 2010-01-28 |
TW201009858A (en) | 2010-03-01 |
WO2010011559A1 (en) | 2010-01-28 |
CN101635512A (zh) | 2010-01-27 |
TW201012040A (en) | 2010-03-16 |
TW201009358A (en) | 2010-03-01 |
TW201106603A (en) | 2011-02-16 |
TW201014137A (en) | 2010-04-01 |
CN102165679B (zh) | 2014-07-02 |
CN102165679A (zh) | 2011-08-24 |
EP2313965B1 (en) | 2017-01-18 |
TWI456206B (zh) | 2014-10-11 |
CN101635524B (zh) | 2014-02-19 |
US8553430B2 (en) | 2013-10-08 |
US20100020573A1 (en) | 2010-01-28 |
CN101635524A (zh) | 2010-01-27 |
US8847719B2 (en) | 2014-09-30 |
US8330434B2 (en) | 2012-12-11 |
EP2313965A1 (en) | 2011-04-27 |
CN101651424B (zh) | 2014-03-12 |
US20100019874A1 (en) | 2010-01-28 |
CN101707121B (zh) | 2013-05-08 |
CN101707121A (zh) | 2010-05-12 |
TWI469487B (zh) | 2015-01-11 |
US20100020570A1 (en) | 2010-01-28 |
TWI452817B (zh) | 2014-09-11 |
US20100020579A1 (en) | 2010-01-28 |
TWI473126B (zh) | 2015-02-11 |
EP2313965A4 (en) | 2015-11-04 |
US8279628B2 (en) | 2012-10-02 |
CN101635512B (zh) | 2014-03-12 |
TWI465026B (zh) | 2014-12-11 |
US8014176B2 (en) | 2011-09-06 |
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