CN1083197C - 同相/正交相正交调制电路 - Google Patents

同相/正交相正交调制电路 Download PDF

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CN1083197C
CN1083197C CN95190187A CN95190187A CN1083197C CN 1083197 C CN1083197 C CN 1083197C CN 95190187 A CN95190187 A CN 95190187A CN 95190187 A CN95190187 A CN 95190187A CN 1083197 C CN1083197 C CN 1083197C
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multiplier
circuit
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CN1124554A (zh
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C·佩西科
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Koninklijke Philips NV
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/32—Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
    • H04L27/34—Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
    • H04L27/36—Modulator circuits; Transmitter circuits
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03C—MODULATION
    • H03C1/00—Amplitude modulation
    • H03C1/52—Modulators in which carrier or one sideband is wholly or partially suppressed
    • H03C1/54—Balanced modulators, e.g. bridge type, ring type or double balanced type
    • H03C1/542—Balanced modulators, e.g. bridge type, ring type or double balanced type comprising semiconductor devices with at least three electrodes
    • H03C1/545—Balanced modulators, e.g. bridge type, ring type or double balanced type comprising semiconductor devices with at least three electrodes using bipolar transistors
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
    • H03D7/14—Balanced arrangements
    • H03D7/1425—Balanced arrangements with transistors
    • H03D7/1433—Balanced arrangements with transistors using bipolar transistors
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
    • H03D7/14—Balanced arrangements
    • H03D7/1425—Balanced arrangements with transistors
    • H03D7/1458—Double balanced arrangements, i.e. where both input signals are differential
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
    • H03D7/16—Multiple-frequency-changing
    • H03D7/165—Multiple-frequency-changing at least two frequency changers being located in different paths, e.g. in two paths with carriers in quadrature
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03C—MODULATION
    • H03C2200/00—Indexing scheme relating to details of modulators or modulation methods covered by H03C
    • H03C2200/0004—Circuit elements of modulators
    • H03C2200/0025—Gilbert multipliers
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03C—MODULATION
    • H03C2200/00—Indexing scheme relating to details of modulators or modulation methods covered by H03C
    • H03C2200/0037—Functional aspects of modulators
    • H03C2200/0058—Quadrature arrangements
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03C—MODULATION
    • H03C2200/00—Indexing scheme relating to details of modulators or modulation methods covered by H03C
    • H03C2200/0037—Functional aspects of modulators
    • H03C2200/0066—Reduction of carrier leakage or the suppression of the carrier
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D1/00—Demodulation of amplitude-modulated oscillations
    • H03D1/22—Homodyne or synchrodyne circuits
    • H03D1/229—Homodyne or synchrodyne circuits using at least a two emittor-coupled differential pair of transistors
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
    • H03D7/18—Modifications of frequency-changers for eliminating image frequencies

Abstract

一种I/Q正交调制/解调电路，供校正一般为LO输入正交信号的相位误差。该电路采用一对吉尔伯单元乘法器，乘法器的底部端口加有I信号和Q信号，乘法器的顶部端口加有和值和差值限幅正交微分信号。其效果在于减小电路对LO相位误差的敏感性，从而改进其排斥边带(图象)的性能，使其比一般采用一个吉尔伯单元乘法器的传统电路还好。

Description

同相/正交相正交调制电路
本发明涉及一种I/Q(同相正交相)正交调/调电路。
发明背景
HPMX-2001通信系统的正交混频器是大家都知道的。例如，有一种硅单片正交移位键控的调制器，其一般的本机振荡器(LO)的工作频率范围为DC-2000兆赫，其一般的I/Q带宽为DC-700兆赫。这类器件的应用场合包括数字蜂窝式无线电话、射频数字链路、矢量发生器、调制器和解调器和单边带混频器。这种和类似芯片的一般I/Q混频器，其性能受到LO信号正交质量的限制。产生正交相位误差的因素有过程上的偏差、电路元件的失配和电路的寄生现象。此外，要制造精确的宽带正交移相器有困难。例如，复数矢量调制/解调器I和QLO信号中的相位误差限制了对满足ADC(IS-54)y GSM数字蜂窝式发信机的系统技术规范至关重要的边带抑制。
发明简介
本发明的目的是性能有所改进的一种正交混频电路。
本发明的另一目的是对正交LO信号中的相位误差基本上不敏感的正交混频电路。
按照本发明的一个方面，本发明的正交混频电路电两个吉尔伯(Gilbert)单元式乘法器组成，各乘法器有若干顶部端口和若干底部端口。和值和差值、限幅正交微分信号加到吉尔伯单元乘法器的顶部端口。其效果是使电路对LO相位误差不太敏感，从而改进其排斥边带(图象)的性能，使其比一般采用一个吉尔伯单元乘法器的传统电路还好。
本说明书所附的构成本说明书的一部分的权利要求书中特别指出了体现本发明特征的在新颖性方面的特点。为了更好地理解本发明、其工作时的优点和通过使用本发明所欲达到的具体目的，应参看附图和说明本发明的一些最佳实施例的说明书。
附图简介
图1是传统的吉尔伯单元乘法器的电路图。
图2的电路图示出了一对等效的微分电路。
图3是本发明中用作正交调制/解调电路的一种形式的混频器的电路图。
图4是本发明另一种形式的正交调制/解调电路的电路图。
最佳实施例详介
吉尔伯单元乘法器是众所周知的。参看例如1977年Wiely出版社出版的Gray和Meyer写的《模拟集成电路》一书第593页。吉尔伯单元乘法器是发射极耦合单元的一种改型，。这种电路使我们可以在IC平稳乘法系统中进行四象限的相乘。图1示出了一般的吉尔伯单元乘法电路10，其特征在于，成对的发射极耦合晶体管Q1、Q2(用编号11表示)与两个交叉耦合的成对晶体管Q3、Q4和Q5、Q6(分别用编号12和13表示)串联连接。这里配备了供LO信号用的两个顶部端口16、17和供射频信号用的两个底部端口18、19。该参考书还详细说明了这种乘法器的工作情况，这里也包括进来以供参考，但为理解本发明的内容，这里没有必要重复该参考书的详细内容。应该指出的是，LO信号系施加得使正信号加到每一对晶体管的两个外晶体管Q3、Q6上，负信号加到每对晶体管的两个内晶体管Q4、Q5上。
为简明起见，每个晶体管对可用一个方框代替，因而图2左侧画出的电路片段与右侧的电路片段(这里称之为微分对)等效。因此，方框20对应于各晶体管对11、12和13。
图3示出了本发明一种形式的正交调制/解调电路，图中同样的编号表示同样的元件。图3和图1不同的地方在于，配备了两个相同的吉尔伯单元乘法器21、22各乘法器，除信号的连接例外，都和图1的电路10一样。图3的电路中，左下侧微分对的端口30、31上加的是正和负I(相同)信号，以VI表示。右下侧微分对的端口32、33上加的是正和负Q(正交)信号，以VQ表示。左微分对左侧的上端口34、35上加的正和负的信号，以V1表示。左微分对右侧的上端口36、37上加的正和负的信号，以V2表示。右微分对左侧上端口38、39上加的正和负的信号，以V3表示。右微分对右侧上端口40、41上加的正和负的信号。以V4表示。吉伯单元上面的线路45提供的正输出和负输出用Vout表示。这对应于下述求和函数。
按照本发明，V1、V2、V3和V4信号规定为：
V1＝sinW1t-(-cosW1t)＝sinW1t+cosW1t    (1)
V2＝cosW1t-(-sinW1t)＝cosW1t+sinW1t    (2)
V3＝sinW1t-cosW1t                      (3)
V4＝cosW1t-(-sinW1t)＝sinW1t+cosW1t    (4)其中W1为LO频率。
这些信号是作为一般IC移相器的正交输出提供的，对应于那些加到图1吉尔伯单元乘法器上端口的正负LO信号即输入到该IC移相器中。从(1)至(4)式可以求出正交LO项的和值项和差值项。可以证明，虽然(1)至(4)式中引入了相位误差项，但本发明调制/解调器结构的独特性能本来就能在正交LO信号只含有相位误差时校正这些误差。因此，正交LO信号的幅值应保持基本上相等。这是借助于正交移相网线路一部分的限幅放大器实现的，该放大器如图4中所示，下面即将说明。
为说明本发明电路的工作情况，要研究一下调制波形。V1、V2、V3和V4的幅值大(＞5VT)得足以转换正交乘法器的上微分对，使其导通/截止。由于V1至V4的限幅作用转换若干VT，因而可以在调制(对V1、V2和V3、V4)端口上以及正交乘法器的线性端口信号(微分V1和VQ)上采用傅里叶级数展开，这里假设V1至V4的幅值大得足以将微分C1和VQ输入信号交替乘法+1和-1倍。
乘法器21和乘法器22的信电极电流加在一起，根据输出电流的相位(+/-180°)消除上/下边带。
正交乘法器的输出为：
Vout＝K3[V1(t)V1(t)]-K4[V3(t)VQ(t)]    (5)＝K3∑AnSin(nW1t+45°)V1(t)-K4∑AnSin(nw1t-45°)Ve(t)    (6)其中An＝(sin(nπ/2))/(nπ/4)               (7)K3＝K3＝K是乘法器人小信号输入端到输出端的增益值。设    V1(t)＝AsinWmt    (8)且    Ve(t)＝AcosWmt    (9)将(8)式和(9)式代入(5)式中，得出：Vout＝K[∑AnSin(nW1t+45°)(AsinWmt)-AnSin(nW1t-45°)(AcosWmt)    (10)其中    An＝(sin(nπ/2)/(nπ/4)    (11)将三角恒等式代入(10)式中，得出：Vout＝K[∑(1/2AnA)[cos(nW1t+45°-Wmt)-cos(nW1t+45°-Wmt)]-∑(1/2AnA)[sin(nW1t-45°+Wmt)+sin(nW1t-45°-Wmt)]    (12)
只考虑接近W1的各项(其它更高次的项都以滤除掉)，得出Vout＝1/2A1A[cos(W1t+45°-Wmt)-cos(W1t+45°+Wmt)]-sin(W1t-45°+Wmt)-sin(W1t-45°-Wmt)]    (13)采用sin(W1t-45°+Wmt)＝-cos(W1t+45°+Wmt)    (14)和sin(W1t-45°-Wmt)＝-cos(W1t+45°-Wmt)    (15)将(14)和(15)式代入(13)式中，得出：Vout＝1/2KA1A[cos(W1t+45°-Wmt)-cos(W1t+45°-Wmt)+cos(W1t+45°+Wmt)+cos(W1t+45°-Wmt)]    (16)将同类项集中在一起，得出：Vout＝KA1A[cos(W1t-Wmt+45°)]    (17)这是下边带项W1t-Wmt，是我们所要求的，其中
A1＝(sin(π/2))/(π/4)＝4/π)    (18)A为I和Q微分输入信号的输入幅值，K为小信号的乘法器增益。
这证明了，只将正交LO信号加到吉而伯单元对，即使有相位误差存在，也能将边带完全消除掉，与正交LO相位的质量无关，在实际应用中，高达±10°的相位误差也不致产生明显的不希望有的(已消除的)边带。
图4示出了本发明一种形式电路的实施例。吉尔伯单元乘法器21、22及其输出对应于图3的电路。I和IN对应于图3中的+VI和-VI。“N”和“I”表示反相信号，有时在符号上加个线条表示。Q和QN相当于图3的+VQ和-VQ。LO和LON相当于正常的正交LO信号。图4中的这些输入信号经限幅放大器50放大，输入到一般的90度移相器51中，移相器51的输出，即sin和sin1及cos和cos/信号，再在限幅放大器53、54中加以放大，作为输入提供给乘法器21和22。从图中可以看出，这个输入相当于上述信号V1-V4。这样，V1＝sin-cos\＝sin+cos；V2＝cos-sin\＝cos+sin；V3＝sin-cos＝sin-cos；V4＝cos\-sin\＝sin-cos。45处的输出在一般加法器55中加起来，从加法器55的输出端得出信号OUT和OUTN。用作调制器时，其输出为经信号VI和VQ调制过的正交LO信号。用作解调器时，其输出为正交IF信号。
不言而喻，本发明并不局限于图4的具体线路，其它产生加到上述成对的吉尔伯单元乘法器的和值和差值限幅正交微分信号的方法都视为属于本发明的范围内。
虽然本发明是就其一些最佳实施例进行说明的，但不言而喻，本技术领域的行家们都知道，在不脱离上述原理的前提下是可以对上述最佳实施例进行种种修改的，因而本发明并不局限于上述最佳实施例，而是包括这些修改的。

Claims (6)

1.一种I/Q正交混频器，包括：
(a)第一和第二乘法装置；
(b)I输入信号施加装置，供将I输入信号加到第一乘法装置上；
(c)Q输入信号施加装置，供将Q输入信号加到第二乘法装置上；
其特征在于，所述混频器包括：
(d)信号V1和V2施加装置，用以将相位相反的信号V1和V2加到第一乘法装置上；
(e)信号V3和V4施加装置，用以将相位相反的信号V3和V4加到第二乘法装置上；
(f)信号混合装置，用以将第一乘法装置和第二乘法装置的输出信号混合起，其中，所述第一和第二乘法装置是个吉尔伯单元乘法器。
2.如权利要求1所述的I/Q正交混频器，其特征在于，各吉尔伯单元乘法器具有第一和第二微分对串联连接到第三微分对上，所述信号分别加到所述第一、第二和第三微分对上。
3.如1至2任何一权利要求所述的I/O混频器，其特征在于，混合装置有一个加法装置。
4.如权利要求1和2任意之一所述的I/Q正交混频器，其特征在于，所述接收和处理装置包括限幅装置，供限定本机振荡信号的幅值用。
5.如权利要求1和2任意之一所述的I/O混频器，其特征在于，所述接收和处理装置包括一个90度移相器。
6.一种收发机，包括以上任一权利要求所述的混频器。
CN95190187A 1994-01-25 1995-01-20 同相/正交相正交调制电路 Expired - Fee Related CN1083197C (zh)

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US08/186,398 1994-01-25
US08/186,398 US5574755A (en) 1994-01-25 1994-01-25 I/Q quadraphase modulator circuit

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CN1083197C true CN1083197C (zh) 2002-04-17

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EP (1) EP0691057B1 (zh)
JP (1) JPH08508632A (zh)
KR (1) KR100335713B1 (zh)
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DE (1) DE69520983T2 (zh)
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EP0691057A1 (en) 1996-01-10
KR960701546A (ko) 1996-02-24
US5574755A (en) 1996-11-12
JPH08508632A (ja) 1996-09-10
KR100335713B1 (ko) 2002-11-13
DE69520983D1 (de) 2001-06-28
DE69520983T2 (de) 2002-01-10
EP0691057B1 (en) 2001-05-23
WO1995020284A1 (en) 1995-07-27
CN1124554A (zh) 1996-06-12

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