CN1380754A - 改进的adsl兼容离散多音频装置 - Google Patents
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L5/00—Arrangements affording multiple use of the transmission path
- H04L5/003—Arrangements for allocating sub-channels of the transmission path
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B3/00—Line transmission systems
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- H04B3/32—Reducing cross-talk, e.g. by compensating
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L5/00—Arrangements affording multiple use of the transmission path
- H04L5/0001—Arrangements for dividing the transmission path
- H04L5/0003—Two-dimensional division
- H04L5/0005—Time-frequency
- H04L5/0007—Time-frequency the frequencies being orthogonal, e.g. OFDM(A), DMT
Abstract
一种考虑了将数字数据编码并调制到总带宽不低于1.6MHz的离散多音频信号上的传输机制。该调制系统在传输过程中动态地改变所用的子载波以及每一子载波传输的数据量(215,217,219)。在一个实施方案中,多音频编码和调制遵循ATIS北美不对称数字用户线路标准。而且,可以使用子信道带宽大于4.3125KHz的另外的子信道(共512个)。在该系统中,那些高于标准中设定频率的子信道依据子载波选择标准和标准范围之内的同样处理。该系统除了允许数字数据以10~50+MBPS的速率在双绞线上传输2000米以上,还允许在具有明显串音噪声,如T1或E1(215,217,219)时,以6~55MBPS的速率传输1200米。
Description
发明背景
本发明主要涉及多载波、高速率数据信号的传输和接收的系统,特别阐述了具有宽带宽的离散多音频(DMT)系统。
本文撰写时,恰是由ANSI(美国国际标准化组织)委派的标准组织电信信息解决方案联盟(ATIS)完成了在非平衡数字用户线(ADSL)上传输数字数据的标准。这一标准主要是旨在在普通电话线上传送视频数据,虽然它也可以用于其它的不同应用中。该标准是建立在离散多音频传输系统的基础上。传输速率被制定为可以在包括双绞线的普通电话线上以至少6百万比特每秒(即,6+MBPS)的速率传输信息。标准化的离散多音频(DMT)系统在前向(下行)每一4.3125KHZ带宽使用256个“音频”。所谓的下行也就是说,在电话系统的概念里,从交换局(一般是被电话公司所有)到远端局,可以是一个用户端(即,居民或商业用户)。
非平衡数字用户线标准也考虑了在至少608KBPS的数据速率时使用双工的反向信号。也就是上行传输,即从远端局传往交换局。由于数据传输速率在前向上比反向要高得多,非平衡数字用户线路也因此而得名。这在准备用电话线传输视频节目或电视会议信息的系统中尤其有用。举例来讲,该系统潜在的应用可以允许居民用户在电话线上获取象电影这样的视频信息,而无需租借录像带了。另一种可能的应用就是电视会议。
那些熟悉非平衡数字用户线标准化过程的人非常了解,象一般的电话系统一样,大多电话系统都是分成了多个电信服务区域,这些区域都有一个适当的最大电信服务区域(CSA)范围。在美国,这个最大电信区域的范围在使用24型双绞线时,是从“中央交换局”2英里以内,在使用26型线时,是9000英尺。因此,标准化过程中重要的特性之一,就是所选的系统能够在双绞电话线(例如24型双绞线)上,从中央交换局穿过CSA范围发送。这就要求信号衰减量不要太大,并且能够相应地容许串音噪声。
对于数字用户线标准的离散多音频解决方案的一个已知的缺点,是当T1串音噪声出现在同一电缆或相邻电缆时,传输结构很难以可靠的信号达到预定范围的外部界限。例如,T1电路通常以大约1.544M比特/每秒数据速率传送24个语音信道,并且通常会产生很大程度的串音噪声。实际上,T1噪声的出现一般将削减数字多音频信号的范围,使之低于CSA范围,该范围给出了所需功率边界和允许的误码率。因此,似乎就需要一些特殊手段来保证在所有情况下达到覆盖信息范围区域。虽然出现T1噪声的电话系统的种类所占的比例很小,但是它在任何标准的服务中都具有100%的兼容性的重要被广泛接受。当然希望用标准化的技术来保证在所有全部电信服务区域的覆盖。可是,普遍认为由于离散多音频技术的特点,这个范围是不可能全部覆盖的。本发明被认为是串音噪声问题的一个解决方案。尽管问题在具有T1噪声的区域里更加显著,但上述解决方案在出现E1噪声(主要处于北美之外)的电话系统中同样适用。
本发明除了减小串音噪声的问题之外,还提供了很多的优点。例如,在不易受T1或E1串音噪声的区域(这是现有电话系统的大多数),所述的发明允许在现有电话上以10~50MBPS每秒的速率可靠传送数字信息。该系统还允许在上行方向提供更高速传输。熟悉本技术的人可以看到,这些传输速率基本上比当前技术可达到的要高。
发明简述
如上所述,本发明的一个目标就是使用离散多音频传输机制提供一种在有噪声的用户通信线上从信息源发送数字信息的方法。该系统将对数字数据编码,并将编码后的数据调制到全部带宽至少为1.6MHZ的离散多音频信号上去。在一些实施方案中,使用了高于8MHZ的带宽。该通信线被监测而确定至少一个线路质量参数,包括每个子信道的噪声级别,每个子信道响应相应的子载波音频。在调制离散多音频信号时,调制机制将许多因素考虑在内,包括了被检测的线路质量参数,子信道增益参数,以及允许的功率屏蔽参数。该调制系统还可以在传输过程中动态改变所用的子载波以及在每个子载波上发送的数据量,目的是动态改变所用发送数据的子信道和/或在每个子信道上发送的信息量,使之配合特定子载波上线路质量的实时变化,与发送器相应的远端接收器完成对离散多音频信号的接收解调和解码。
在本发明的一个实施方案中,尽管共使用了512个每个具有约4.3125KHZ带宽的子信道,多音频编码基本上是遵循ATIS非平衡数字用户线标准而完成的。在这个实施方案中,那些高于标准中设定频率的子信道依据子载波选择标准和标准范围之内的同样处理。这个实施方案考虑使用具有2.208MHZ带宽的离散多音频信号。在另一个实施方案中,子信道的数量可以在128~2048之间或更多。
在一些实施方案中,每一子信道的带宽被增加了,使总带宽大于4.3125KHZ宽的子信道能够提供的总带宽。例如,每个子信道的带宽可以在5~40KHZ的范围之内,或更宽。在所述的一个实施方案中,考虑了可获得的256个子信道,每个具有34.5MHZ带宽,总可用带宽为8.832MHZ。在容易受到已知受控信源(比如业余无线电信号)干扰的应用中,与干扰相应的波段可以被简单地屏蔽掉,在两个方向都用无声来防止干扰。
在发明的另一个应用中,这可以使用在出现明显串音噪声的系统中。在这样的系统中,信号在具有高于或低于最大串音噪声(例如T1串音噪声)频率的子载波上发送,以实现编码后的数字数据以高于6百万比特每秒(6MBPS)的数据速率通过电信范围区域的传输。
在发明的另一个应用中,本发明可以用普通的电话线,例如双绞线,来将数据以至少一千万比特每秒(10MBPS)的数据传输速率从发送器传送到位于2000米以外的远端接收器。实际上在1000米双绞线距离内超过25MBPS的数据传输速率和600米双绞线内超过50MBPS的速率都是容易获得的。
在发明的另一个应用中,上行通信可以获得额外的带宽,来允许上行通信在任何适当的数据速率上进行。
附图简述:
参看下面对附图的描述,可以更好地理解本发明以及进一步的目标和优越性。
图1所示是根据ATIS北美标准的离散多音频传输波段的图形。
图2所示是典型的比特分布图,它显示了对于具有最严重串音的1公里长26型电话线,在每一音频上传送的比特数。
图3所示是普通T1噪声的频谱。
图4将所述发明可达到的数据速率和依据用于非平衡数字用户线路的ATIS北美标准在26型或24型双绞线、可变距离,相邻电缆上存在T1噪声的情况下来实现离散多音频传送可达到的数据速率相比较。
图5是一个视频发送系统的框图,该系统使用了既适合实现本发明又适合实现ATIS非平衡数字用户线路标准的离散多音频传输机制。
图6所示是适用在许多现有电话系统中的分布区域结构图、
图7所示是对图2典型的比特分布图的改进,用来屏蔽可能的业余无线电波段。
图8是适合实现本发明的收发器的图解框图。
发明详述
现在提出的ATIS非平衡数字用户线路北美标准考虑了使用离散多音频数据传输机制。离散多音频传输机制协议的详细阐述在讨论中的北美标准中有详细描述,该标准指T1E1.4ATIS标准,并且现在在标准稿NO.94-007,rev.8中设定,日期是1995年3月。如图1所示,在北美标准中标准化了的离散多音频系统在前向(下行)使用了256个“音频”,每个4.3123KHZ宽。音频的频率从0~1.104MHZ。较低的32个音频可以用来在上行方向传输双工数据。如应用的背景部分描述的那样,离散多音频传输系统有一个通常被认为是无法解决的局限性,就是无法在存在T1噪声的情况下保证可靠的电信服务区域信号的传输。
这里提供的解决方案可以极大地增加传输带宽。在一个例子中,是通过增加具有相同带宽的子信道数量来实现的。在另一个例子中,是通过增加每个子信道的带宽来实现。也就是,用具有两倍到十倍于建议的带宽的系统来取代建议的标准中(如图1所见)设定的256个子信道1.104MHZ带宽。举例说明,在一个实施方案中,通过提供512个每个都有4.3125KHZ的带宽的子信道来加倍传输带宽,达到2.208MHZ总带宽。在另一个实施方案中,使用8倍数量的4.3125KHZ宽子信道,从而提供了8.832MHZ带宽。如果需要,用于上行传输的可获的子信道数量(及带宽)也可以被增加。分配来作上行传输的带宽可以在一个大的范围中变化,以适应特殊应用需求。用于上行传输的子信道数量可以对ATIS标准中建议的32个音频带宽加倍,成为64个音频。
另一建议是考虑给每个子信道多分配带宽。举例说明,将每个子信道带宽增加2~10倍,将有较好的效果。因此在一个256个子信道的系统中,如果每个“音频”的带宽为34.5KHZ,那么可以提供8.832MHZ的总带宽。当然,对任何特定系统,增加子信道数量和增加音频带宽的方法可以独立使用亦可同时进行。
那些熟悉本技术的人员将看到,ATM设备有一个重要的安装基础,此设备是设为标准的传输速率25.6MBit/sec和/或51.84MBit/sec,这样的数据速率可以很容易的经过许多现有双绞线,直接发送到最终用户,而该双绞线使用了依照本发明的有8.832MHZ传输带宽的离散多音频系统。
在实际应用中,即使是特定的带宽,当使用多个子信道时,通常可以获得更高的数据传输速率。但是多的信道一般会转换为高的硬件开销。相比之下,扩展信道带宽将是一个低开销的解决方案,不过它的最大传输速率将略低一些。
本技术领域的人员可以看到,普遍认为在基本上高于1.1MHZ范围(如高于1.3MHZ)的频率传输将不适合在双绞线上在相当长的距离上传输。但是,在该领域的应用试验表明并不是那样。在离散多音频协议下的传输在1~10MHZ的范围甚至更高,可以顺利进行。例如,图2中的图形所示25.6Mbit/sec传输系统的典型比特分布图,该系统没有包括回声抵消。所示的实施方案表明了在具有最严重串音的1公里长26型电话线上每个音频上传输的比特数。这种情况下的富余度是约12.4分贝,远高于一般认为数字数据传输所需的富余度(通常最小富余度为6分贝)。如图所示,在高于1.1MHZ频率时数据传输良好。
下面参看图3,将阐述本发明在存在T1噪声的电信服务区域中的实用性。在文中可看到,T1噪声在相对低的频率(如在低于600KHZ频率时),并不是一个非常大的因素。然而,它的干扰(串音)程度随着频率的增大而增加,直到超过了从中央交换局到一公里以外的地点的离散多音频传输所能接受的指标。因此,通常认为在存在T1噪声的电信服务区域,离散多音频传输不能被可靠地用在高于600~750KHZ频率的子信道里。尤其是远端局位于离信源距离超过1公里的情况下,更是这样。这样,T1噪声极大地限制了在前向方向上可用来作数据传输的子信道数量,如图4中图形显示的那样,它严重地限制了数字数据可被传输的速度。不过如图3所见,在高于约1.3MHZ的频率上,由T1噪声产0生的串音量开始明显下降。T1噪音曲线的第二个峰值在高于1.6MHZ时开始明显。所以在1.3~1.6MHZ范围内的子信道的T1串音噪声相对较小。因此,当如上文所述使用更宽的512个子信道带宽,就可以在相邻(甚至同一)电缆上存在显著的T1噪声的情况下,可靠地达到6MBPS的数据传输速率。
从事本技术的人可以看到,这克服了用于北美非平衡数字用户线路服务的离散多音频传输标准中最多争议的缺点。在任何特定的时间根据噪声的情况以及数据传输的需求,实际的传输带宽可以从一种传输到另一种传输有很大变化。不过,似乎在出现T1噪声时,大多数的数据传输将在50和600KHZ之间以及1.3到1.6MHZ的带宽中进行。由于传输主要是在不与T1传输冲突的频段中进行,使用这一更高的频段具有不在周围线路上感生同样噪声的附加收益。
由依据发明的上述加倍子信道的实施方案工作的离散多音频发射器获得的数据速率将参照图4作描述。图4将双倍带宽实施方案与依据用于非平衡数字用户线路的ATIS北美标准在26型或24型双绞线、可变距离,在相邻电缆上存在T1噪声的情况下来实现离散多音频传送可达到的数据速率相比较。这里可以看到,在出现T1噪声时,所述发明显著地提高了数据传输速率。
以上的文字描述了在存在T1串音噪声的系统中本发明的应用。但是应当看到所述的系统可以同样有效地防止高次T1噪声,E1串音噪声(在欧洲国家出现更多,并且在800~1700MHZ范围中最严重),业余无线电干扰(其占据了2M~30MHZ的一些窄波段)以及任何其它的噪音,无论它是官方的还是本地的。所述的离散多音频系统简单地避免了存在噪声和/或干扰问题的频段。它具有两个好处,一是使用有噪声的子信道不影响系统本身的传输,二是不会干扰其它可能落在传输介质可用频率大范围之内的启用频段。
通过举例,下面将描述在同时存在业余无线电广播的系统中本发明的应用。图7显示了上述离散多音频系统的典型比特分布,参看图2,将传输业余无线电的相应频段简单地屏蔽掉。也就是,在所示实施方案中,三个窄带215,217和219被简单地屏蔽掉,这样离散多音频系统在被屏蔽的频率范围就不传送。应当看到,屏蔽对系统的数据传输能力不会改变太多。在列举的实施方案,被屏蔽掉的波段包括1.81~2.0;3.5~3.8和7.0~7.1MHZ频段。与图2表示的上述系统相比较,获得同样的25.6Mbit/sec数据传输速率,只是在富余度上下降了约一分贝。而这样的富余度远高于通常认为这类数据传输系统所必需的6分贝富余度。
所述的结构还有其它的一些优点。最值得一提的是,在没有出现串音噪声的系统中(北美大部分现有的电话系统),可以可靠地达到更高的数据传输速率。举例来讲,在上文提到的双倍带宽的例子中,在传送6000英尺距离双绞用户线上,可以可靠地获得至少12MBPS的数据速率。进而,当反向传输可用的子信道数也加倍时,反向可达数据传输速率也可以显著提高。例如,可以很容易获得至少1.544MBPS(即T1数据传输速率)的传输速率、
如本技术领域的人员所见,特定系统获得的数据传输速率是一些变量的函数。这些变量包括了信号必须经过的传输线的距离,传输线的特性,所需的富余度,发射器功率级别,以及加入的噪声。因此,通常信号传输距离较短,线路质量较高,噪声较小的系统可以处理较高的数据传输速率。另一方面,必须较长距离传输,经过较高型号双绞线,噪声较多的系统通常将限制在相对较低的传输速率上。
在没有引入回声抵消因而应用较低的频率来完成上行通信的系统中,离信源1000米的双绞线上容易获得25MBPS或更高的数据传送速率。例如,在24型双绞线上传输25.6MBPS并且留有6分贝富余度的系统需要15dbm发送机功率来达到,1000米的范围。在回波抵消系统中,很容易在距信源600米的双绞线上获得50MBPS或更高的传输速率。举例说明,在24型双绞线上以51.84Mbps发送并保留6dB富余度的系统需要大约15dbm的发射机功率,以达到600米的范围。如上文所述,实际的传输速率的大小将依据特定系统的特性而有极大的变化。当然,本领域的人员应该知道,所述的系统允许数字数据在现在以电话为基础的基础设施中,以比现有技术高得多的传输速率发送。
为了更好地说明所述发明的能力,下面将描述发明在使用光纤传输线的另一个现有电话系统结构中的应用。图6显示了一个这样的结构。在该结构中,一个光纤馈线200被用来服务于多个光网络单元202。每个光网络单元通过可达1500米长的双绞分布线206与多个配线架204相连接。每个配线架能用于多个分支线208,这些分支可以接居民单元,商业单元,等等。通常从双绞线形成的分支208一般不超过50米长。所以应该看到,发明可以用来对现有结构的数据传输速率作很大提高。
下面再参看图5,将描述一个依照本发明工作的视频发送系统。视频服务器21通过一台异步转移模式交换机22向发射器20提供数字数据。视频服务器21可以提供任何速率数据,大到根据传输距离,线路质量及使用的通信线类型所允许的最大数据率。发射器20包括一些组成部分,有一个编码器23和一个离散多音频调制器25。编码器23完成复用、同步、编码和压缩视频数据,而且能处理高达15M比特每秒的数据速率。特别是,它可以为许多子信道中的每一个将输入比特流转换成同相位、正交的分量。编码工作可以用前向纠错和/或格状编码来完成。在所述实施方案中,可用512个子信道。这样,编码器输出512个子符号序列,每个代表4KBPS。输入信号是多路输入,它们被送往离散多音频调制器25。通过举例,将详细描述参照ATIS标准的适当的编码器。
调制器25是一个IFFT调制器,它用适当的算法来计算反向傅立叶变换。由于编码器输出是复数,IFFT调制器接收1024个输入。比特分布在所述的,离散多音频系统中参照ATIS标准被合理地确定。为实现这一点,发射器20还包括了一个线路监测器64(见图8),来监测每个可用子信道的线路质量。在一个实施方案中,线路监视器决定了在每个子信道中的噪声级别,信号增益和相位漂移。目的是为每个子信道估算信噪比。因此,其它的参数也可以一同被监测,或替代上述参数被监测。哪些子信道被用来发送编码后的数据以及每个子信道上传送多少数据是依据一些因素动态决定的。这些因素包括被检测的线路质量参数,子信道增益参数,以及允许的功率屏蔽参数,及适当的最大子载波误码率。要强调的是,子信道间的各种因素不必要是常数,且实际上在使用期间是可用变化的。尤其更说明的是,这些线路质量参数是连续监测的,并且在调制机制中,调整是实时进行的,以期当不同子信道线路质量在使用中变化时动态调节调制设备。例如,在同一ATIS标准中描述了一个适当的离散多音频调制器。
在编码信号被调制,形成离散多音频信号后,循环前缀被加到离散多音频编码信号上。该循环前缀主要是用来简化离散多音频信号的解调。在ATIS标准中,使用了32位循环前缀。当然,在所述实施方案中较大带宽的情况下,也可以加倍循环前缀的长度。发送器还包括了一个数模转换器和线路驱动器28,它将离散多音频信号加到通信线40(图8中的传输介质40)上,该线路可以是双绞电话线。当然,其它传统的通信线也可以使用。由于双绞线在现有通信系统中被广泛使用,所以对它尤其感兴趣。
带有循环前缀的离散多音频编码信号然后经过通信线40(图8中的传输介质40)被发送到远端局。在所述的512个子信道的实施方案中,离散多音频信号共有约2.208MHZ的可用带宽。在一个实施方案中,发送器位于电信业务服务区域中的中央交换局,通信线是双绞线信道。在另一个实施方案中可以用不同的通信线路。
然后,信号被位于远端局的接收器30接收。接收器有一个模拟滤波器32,一个时域均衡器38(TEQ),一个解调器31来解调均衡后的离散多音频信号并分离循环前缀,以及一个解码器33来对解调后的信号解码。解调器31和解码器33分别完成与调制器25和编码器23相反的功能。解码后的信号再从解码器33被送往远程单元36,诸如电视,计算机或其它适当的接收装置。时域均衡器,解调器31和解码器33的功能,包括适合完成制定功能的算法,都在Chow et al的美国专利NO.5,285,474中有更详细的描述。
上行编码和调制可以与所述的下行数据传输使用完全相同的方法。不过,
上行编码和调制可以与所述的下行数据传输使用完全相同的方法。不过,在所述实施方案中,只有64个子信道可用来作上行传输。但应该知道,对这样的上行通信可以使用任何数量的子信道。
在一些所述的实施方案中,子信道带宽被认为是固定的。但在一些应用中,可以提供一种机制,用来动态地同步调节子信道的带宽。在这样的系统中,固定数量的子信道获得的数据传输速率可以仅仅通过加宽子信道带宽来增加。例如,一个典型的系统可以包括256个子信道,每个信道的带宽可以在4.3125KHZ~34.5KHZ的范围内变化。当然,实际范围可以根据特定系统的需求作大范围的变化。在一个这样的结构中,系统可以初始设置在子信道带宽小的情况下。然后,当系统的负荷增加,子信道带宽可以按照要求逐渐调节,去处理增加的数据传输需求。一般来讲,带宽增加的步骤只是不不经常地进行,并被认作是系统升级。在另一个实施方案中,带宽可以动态地增加或减小,来满足系统当前数据传输的需要。
虽然这里只描述了本发明的几个实施方案,应该知道,在不离开发明的思想和范围的情况下,本发明还可以用其它的特定形式来实现。特别是,本发明按照与建议的ATIS北美不对称数字用户线标准兼容的实施方案来描述、当然,应当看到,发明对无论是对称还是不对称的离散多音频传输结构是同样可用的。发明并不仅仅局限于具有在所述实施方案中使用的特定子信道带宽的传输结构,它容易被应用在很大范围的传输结构中。重点是数据可以被可靠地在电话线上,在信道频率高于过去认为的可传输频率的子信道中传输。另外,根据本文,列举的实例只是为了便于说明,并不是严格的,而且发明也并不局限于这里的具体描述,而是可以在所附权利要求范围内作更改。
Claims (3)
1.一种离散多音频接收器,用于通过双绞线型通信线接收第一组多音频编码数字信息,该接收器包括:
一个解调器,用于解调由多个子载波而来的编码数字信息,该信息在离散多音频信号中,具有高于6M比特/每秒的数据速率,每一个子载波与相应的音频和子信道相对应,其中对离散多音频编码信号可用的子载波具有至少1.6MHZ的合成带宽,解调器被调整来接收作为部分离散多音频信号的调制信息,其中解调器可以在接收期间,为了配合调制结构中的实时变化,动态地改变以响应变化了的调制信息,解调器被用来分离离散多音频信号的循环前缀;
一个解码器,用来实时将解调后的数字信息解码;
一个编码器,用于对第二组数字信息进行编码;
一个调制器,用来将编码后的第二组数字信息以第二离散多音频信号的形式调制到多个子载波上,每个第二离散多音频信号的子载波与相应的音频和子信道相对应,其中对于编码的第二离散多音频信号可用的子载波合成带宽比编码的第一离散多音频信号可用的子载波带宽低得多。
2.如权利要求1所述的接收器,其特征在于,所述编码的第二离散多音频信号具有多达64个独立的子载波,并且通过通信线被发送至信源。
3.如权利要求1所述的接收器,其特征在于,所述解调器还包括了一个时域均衡器。
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DE69532076T2 (de) | 2004-04-22 |
EP0755601B1 (en) | 2003-11-05 |
EP0755601A4 (en) | 1999-09-01 |
AU691919B2 (en) | 1998-05-28 |
CA2187753A1 (en) | 1995-10-26 |
FI964038A (fi) | 1996-10-09 |
DE69532076D1 (de) | 2003-12-11 |
CN1149360A (zh) | 1997-05-07 |
CN1080030C (zh) | 2002-02-27 |
FI964038A0 (fi) | 1996-10-09 |
FI114059B (fi) | 2004-07-30 |
KR970702625A (ko) | 1997-05-13 |
US5519731A (en) | 1996-05-21 |
AU2389395A (en) | 1995-11-10 |
CN1529492A (zh) | 2004-09-15 |
JP3452932B2 (ja) | 2003-10-06 |
US5673290A (en) | 1997-09-30 |
EP0755601A1 (en) | 1997-01-29 |
KR100336144B1 (ko) | 2002-09-27 |
CN1193507C (zh) | 2005-03-16 |
JPH10503624A (ja) | 1998-03-31 |
CA2187753C (en) | 2005-10-18 |
WO1995028773A1 (en) | 1995-10-26 |
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