US20040164886A1

US20040164886A1 - Data driver

Info

Publication number: US20040164886A1
Application number: US10/459,479
Authority: US
Inventors: Wei-Chieh Hsueh
Original assignee: Toppoly Optoelectronics Corp
Current assignee: Innolux Corp
Priority date: 2003-02-21
Filing date: 2003-06-12
Publication date: 2004-08-26
Anticipated expiration: 2023-06-12
Also published as: TW200416653A; TW594634B; JP2004252404A; JP3949617B2; US6788231B1

Abstract

A data driver for driving pixels in an active matrix organic LED (AMOLED) is provided. The data driver includes a plurality of converters configured to convert to analog current signals from digital voltage signals in order to drive the pixels to emit light. Each converter has a plurality of current mirror devices configured to generate mirrored current signals by inputting two control signals. Meanwhile, the mirrored current signals can maintain their preciseness even if deviation of the characteristics of the transistors implanted within the current mirror devices occurs during fabricating.

Description

This Application claims priority to Taiwan Patent Application No. 092103685 filed on Feb. 21, 2003.

FIELD OF INVENTION

The present invention relates to a data driver for an active matrix organic light emitting display (AMOLED), which is configured to convert digital voltage signals into analog current signals to drive pixels in the display to emit light.

BACKGROUND OF THE INVENTION

Pixels in an AMOLED are driven by analog current signals; however, the signals that control the pixels to emit light are digital voltage signals. Therefore, each AMOLED needs a data driver (or source driver) to convert digital control voltage signals into analog current signals.

FIG. 1 illustrates a

data driver

1 of the prior art. As it shows, the data driver 1 includes a first shift register 101, a data register 103, a voltage latch 105, a converter 107, a current latch 109, a current source 111, and a second shift register 113. The converter 107 is configured to receive the digital voltage signals 110, which will later drive pixels to emit light, from the voltage latch 105, and to convert the digital voltage signals 110 into analog current signals 112 based on the reference currents provided by the current source 111. The second shift register 113 is configured to switch on or off each cell in the current latch 109 in order to store the analog current signals 112 sent by the converter 107. After a proper period of time, an enabling signal 108 enables the current latch 109 so that all the analog current signals 114, identical to the analog current signals 112, are able to reach all pixels of the AMOLED to present a transient frame.

The framework of the

converter

107 is basically a current mirror. FIG. 2 illustrates one kind of current mirror of the prior art. With reference to FIG. 2, a reference current I_s, generated by the current source 111 shown in FIG. 1, mirrors I_p1, I_p2, I_p3, etc. through a transistor MP1. It is noted that the values of the mirrored currents, e.g. I_p1, I_p2, I_p3, etc., are associated with the characteristics, i.e. aspect ratio, threshold voltage, and mobility, of MP2, MP3, MP4, etc. Once any deviation from the theoretical characteristics of the transistors is induced during fabricating, the practical values of the mirrored current I_p1, I_p2, I_p3etc. will bring error as well. The error, even if it is tiny, might still influence the gray level that an analog current signal actually sets in due to the narrow band of each gray level and, therefore, pixels might emit unexpected illumination.

SUMMARY OF THE INVENTION

The present invention discloses a data driver for an active matrix organic light emitting display (AMOLED), which converts digital voltage signals into analog current signals in order to drive all pixels in the display to emit light.

The data driver includes a first shift register, a data register, a data latch, a second shift register, and N converters. The first shift register is configured to provide an N-bit first control signal. The data register is configured to store N M-bit digital voltage signals by switching on the cells in it in turn in response to the first control signal, and to send the N digital voltage signals to the data latch. The data latch is configured to receive the N digital voltage signals and respectively transmit them to the N converters in response to an enabling signal. The second shift register is configured to provide an (M+1)-bit second control signal to control the procedure of converting the digital voltage signals into analog current signals.

Each converter of the data driver of the present invention is a digital-voltage-to-analog-current converter with M units regarded as current sources. Each current source (or each unit) includes two control signals to enable or disable the transistors within so as to control the generation timing of mirrored currents. The current source can overcome the drawbacks of the prior art and, therefore, the mirrored current does not deviate even if the characteristics of the transistors within have been changed during fabricating.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 illustrates a data driver of the prior art. [0009]
FIG. 2 is the exemplary circuitry of a current mirror of the prior art. [0010]
FIG. 3 illustrates the data driver of the present invention. [0011]
FIG. 4 illustrates the converter of the present invention. [0012]
FIG. 5 is the circuitry of a current mirror of the present invention.[0013]

DETAILED DESCRIPTION

With reference to FIG. 3, the [0014] data driver 2 disclosed by the present invention includes a first shift register 201, a data register 203, a data latch 205, a second shift register 207, and N converters 209. The first shift register 201 is configured to receive a data shift signal 202 and provide an N-bit first control signal 204. The first control signal 204 is transmitted to the data register 203 to switch on the cells in the data register 203 so that N M-bit digital voltage signals 206 are stored in turn. The digital voltage signals 206 are the signals that need to be converted into analog current signals 218, which are then respectively transmitted through data lines to drive pixels and make pixels emit light. After receiving and storing all of the digital voltage signals 206, the data register 203 will send these signals 206 to the data latch 205. The data latch 205 is switched on by an enabling signal 210 at a particular timing so that the digital voltage signals 208, identical to the digital voltage signals 206, are able to be transmitted to N converters 209 respectively. The second shift register 207 is configured to provide an (M+1)-bit second control signal 216 in response to a signal 214 to activate the procedure of converting digital voltage signals 212, identical to the digital voltage signals 208, to analog current signals 218 in N converters 209. The converters 209 are digital-voltage-to-analog-current converters with the same function that the current latch 109 shown in FIG. 1 has. Each of the converters 209 is capable of seizing the converted analog current signals 218 and does not release them to pixels until all of the digital voltage signals 212 have been converted.
To specify one preferred embodiment of the [0015] converters 209 of the present invention, each digital voltage signal is assumed to be a 6-bit signal. As shown in FIG. 4, each of the N converters 209, responsive to a 6-bit input, is required to have 6 first devices 301 and 6 second devices 303. Each first device 301, responsive to one of the preceding 6 bits SW₀˜SW₅of the second control signal 216, is configured to generate one of the 6 first mirrored currents I_m0˜I_m5respectively, and to transmit it to the corresponding second device 303. Each second device 303, responsive to both a last bit SW₆of the second control signal 216 and one of the 6 first mirrored currents I_m0˜I_m5, is configured to generate one of the 6 second mirrored currents I₁₀˜I₁₅. Finally, the specific digital voltage signal 212 is converted into an analog current signal 218 when all of the 6 second mirrored currents I₁₀˜I₁₅are added together.
Take the [0016] unit 3 shown in FIG. 4 as an example, the first device 301 converts the reference current I_ref1provided by the current source 211 into a first mirrored current I_m1after receiving the second bit SW₁of the second control signal 216. The second device 303 then converts the first mirrored current I_m1into a second mirrored current I₁₁, according to the value of the second bit D₁of the specific digital voltage signal 206 while receiving the last bit SW₆of the second control signal 216.
The [0017] current source 211 of the embodiment has at least 6 outputs so that it provides 6 different reference currents I_ref0˜I_ref5for the 6 first devices 301 to respectively generate the 6 first mirrored currents I_m0˜I_m5. The value of each 6 referent currents I_ref0˜I_ref5is 2 times larger than that of each preceding one. If I_ref0=2 μA, for example, then I_ref1=4 μA, I_ref2=8 μA, I_ref3=16 μA, I_ref4=32 μA, and I_ref5=64 μA. Assuming that one of the digital voltage signals is (D₅D₄D₃D₂D₁D₀)=(101001), the corresponding analog current signal I_TOTALgenerated by the converter 209, as shown in FIG. 4, will equal IM0+I_m3+I_m5=I_ref0+I_ref3+I_ref5=82 μA.
FIG. 5 illustrates the circuitry of the [0018] unit 3 shown in FIG. 4. The converter 209 can provide a high level voltage source VDD and a low level voltage source VSS externally or internally. The first device 301 includes a first transistor M1, a second transistor M2, a third transistor M3, and a first capacitor C1. The first transistor M1 and the second transistor M2 are n-channel TFTs, and the third transistor M3 is a p-channel TFT. All of the transistors M1, M2, and M3 include a source, a drain, and a gate respectively. Since there is no difference between the source and the drain of a TFT, both are renamed as a first terminal and a second terminal in the following description to avoid misunderstanding. The first capacitor C1 includes a first end 1 st and a second end 2nd. The interconnections within the first device 301 include: the gate G of the first transistor M1 is configured to input the second bit SW₁of the second control signal 216, the second terminal 2nd of the first transistor M1 is connected to the second output I_ref1of the current source 211, the first terminal 1 st of the first transistor M1 is respectively connected to the first terminal 1 st of the second transistor M2 and the second terminal 2nd of the third transistor M3, the gate G of the second transistor M2 is connected to the gate G of the first transistor M1, the second terminal 2nd of the second transistor M2 is respectively connected to the gate G of the third transistor M3 and the second end 2nd of the first capacitor C1, and the first end 1 st of the first capacitor C1 is respectively connected to the first terminal 1 st of the third transistor M3 and the high level voltage source VDD.
The [0019] second device 303 includes a fourth transistor M4, a fifth transistor M5, a sixth transistor M6, a seventh transistor M7, and a second capacitor C2. The transistors M4˜M7 are all n-channel TFTs having a first terminal 1 st, a second terminal 2nd, and a gate G. The second capacitor C2 includes a first end 1 st and a second end 2nd. The interconnections within the second device 303 include: the gate G of the fourth transistor M4 is configured to input the last bit SW₆of the second control signal 216, the second terminal 2nd of the fourth transistor M4 is connected to the second terminal 2nd of the third transistor M3 of the first device 301, the first terminal 1 st of the fourth transistor M4 is respectively connected to the first terminal 1 st of the fifth transistor M5 and the second terminal 2nd of the sixth transistor M6, the gate G of the fifth transistor M5 is connected to the gate G of the fourth transistor M4, the second terminal 2nd of the fifth transistor M5 is respectively connected to the gate G of the sixth transistor M6 and the second end 2nd of the second capacitor C2, the first end 1 st of the second capacitor C2 is respectively connected to the first terminal 1 st of the sixth transistor M6 and the low level voltage source VSS, the first terminal 1 st of the seventh transistor M7 is connected to the second terminal 2nd of the sixth transistor M6, and the gate G of the seventh transistor M7 is configured to input the second bit D₁of the 6-bit digital voltage signal 212.
The second bit SW[0020] ₁of the second control signal 216 is used to enable or disable the first transistor M1 and the second transistor M2. When SW₁is high, the first transistor M1 and the second transistor M2 are enabled so that the second reference current I_ref1provided by the current source 211 is able to flow through the first transistor M1 and the third transistor M3 and hence charge the first capacitor C1. In other words, the second reference current I_ref1is converted into a corresponding first voltage stored in the first capacitor C1. After the first capacitor C1 is fully charged, SW₁will switch to a low level so that the first transistor M1 and the second transistor M2 are disabled and, therefore, the first voltage is saved in the first capacitor C1.
The last bit SW[0021] ₆of the second control signal 216 is used herein to enable or disable the fourth transistor M4 and the fifth transistor M5. When SW₆is high, the fourth transistor M4 and the fifth transistor M5 are enabled so that the first voltage stored in the first capacitor C1 is able to convert into a second voltage stored in the second capacitor C2. After the second capacitor C2 is fully charged, SW₆switches to a low level to disable the fourth transistor M4 and the fifth transistor M5 and, therefore, the second voltage is saved in the second capacitor C2. If the second bit D₁of the digital voltage signal 212 transmitted to the converter 209 shown in FIG. 4 is high, the second voltage will be converted into the second mirrored current I₁₁flowing through the sixth transistor M6 and the seventh transistor M7. Otherwise, the transistor M7 will be off and the second mirrored current I₁₁will not appear.
The equation showing the relation of the current and the potential difference between the gate and the source of a field effect transistor (FET) in a saturation region is [0022] $i_{D} = \frac{1}{2} μ C_{OX} \frac{W}{L} {(v_{GS} - V_{t})}^{2}$
According to this equation, when the first capacitor C[0023] 1 is in charging mode, the second reference current I_ref1can be converted into a corresponding V_GSstored in the first capacitor C1 regardless of the practical aspect ratio, threshold voltage, or mobility of the third transistor M3. When SW₆is high, the V_GSstored in the first capacitor C1 is converted into the first mirrored current I_m1to charge the second capacitor C2 through the transistors M3, M4, and M6. Because the V_GSstill biases on the third transistor M3, the value of the second mirrored current I₁₁is substantially equal to that of the first mirrored current I_m1, i.e. equal to the reference current I_ref1.
Based on the aforementioned function of the [0024] unit 3, one can appreciate that the unit 3 is a current mirror. In this current mirror, SW₁is regarded as a first control signal for enabling or disabling the first transistor M1 and the second transistor M2; SW₁also assures that the reference current I_ref1be converted into the first voltage stored in the first capacitor C1. Moreover, SW₆is regarded as a second control signal for enabling or disabling the fourth transistor M4 and the fifth transistor M5; SW₆assures that the first voltage be converted into the corresponding second voltage stored in the second capacitor C2. The second mirrored current I₁₁is then generated in reference to the second voltage, i.e. in reference to the reference current I_ref1. The framework of the current mirror of the present invention has an advantage of generating a steady mirrored current without respect to the characteristics of the transistors within.
The frameworks and functions of other units shown in FIG. 4 are identical to those of the [0025] unit 3. As FIG. 4 shows, the second terminals of all the seventh transistors M7 of the second device 303 are respectively connected to a common node n1. A sum I_TOTALof all the currents flowing through the common node n1 is one of the analog current signals 218, which drives one pixel in an AMOLED to emit light. There are N converters 209 provided by the present invention to drive N pixels in an AMOLED to emit light simultaneously.
As set forth above, the data driver of the present invention is capable of converting digital voltage control signals for controlling pixels to emit light into analog current signals that can drive OLEDs directly. Moreover, the data driver of the present invention is capable of generating steady analog current signals even if the characteristics of the transistors within deviate from theoretical values during fabricating. [0026]

Claims

1. A data driver of an active matrix organic light emitting display (AMOLED), comprising:

a first shift register configured to provide an N-bit first control signal;

a data register configured to store N M-bit digital voltage signals responsive to the first control signal;

a data latch configured to receive and transmit the N digital voltage signals in response to an enabling signal;

a second shift register configured to provide an (M+1)-bit second control signal; and

N converters, each of the n converters comprising:

M first devices, respectively responsive to preceding M bits of the second control signal, configured to generate M first mirrored currents respectively; and

M second devices, responsive to a last bit of the second control signal and the M first mirrored currents, configured to convert one of the N digital voltage signals into an analog current signal.

2. The data driver of claim 1, wherein after the data latch receives all of the N digital voltage signals from the data register, the enabling signal enables the data latch in order to transmit the N digital voltage signals to the N converters respectively.

3. The data driver of claim 1, wherein the data driver further comprises a current source having at least M outputs for providing M different reference currents for the M first devices to generate the M first mirrored currents.

4. The data driver of claim 3, wherein each converter further comprises a high level voltage source and a low level voltage source, and each of the M first devices comprises:

a first transistor, comprising a first terminal, a second terminal, and a gate;

a second transistor, comprising a first terminal, a second terminal, and a gate;

a third transistor, comprising a first terminal, a second terminal, and a gate; and

a first capacitor, comprising a first end and a second end;

wherein the gate of the first transistor is configured to input one of the preceding M bits of the second control signal, the second terminal of the first transistor is connected to one of the M outputs, the first terminal of the first transistor is respectively connected to the first terminal of the second transistor and the second terminal of the third transistor, the gate of the second transistor is connected to the gate of the first transistor, the second terminal of the second transistor is respectively connected to the gate of the third transistor and the second end of the first capacitor, and the first end of the first capacitor is respectively connected to the first terminal of the third transistor and the high level voltage source.

5. The data driver of claim 4, wherein each of the M second devices comprises:

a fourth transistor, comprising a first terminal, a second terminal, and a gate;

a fifth transistor, comprising a first terminal, a second terminal, and a gate;

a sixth transistor, comprising a first terminal, a second terminal, and a gate;

a seventh transistor, comprising a first terminal, a second terminal, and a gate; and

a second capacitor, comprising a first end and a second end;

wherein the gate of the fourth transistor is configured to input the last bit of the second control signal, the second terminal of the fourth transistor is connected to the second terminal of the third transistor, the first terminal of the fourth transistor is respectively connected to the first terminal of the fifth transistor and the second terminal of the sixth transistor, the gate of the fifth transistor is connected to the gate of the fourth transistor, the second terminal of the fifth transistor is respectively connected to the gate of the sixth transistor and the second end of the second capacitor, the first end of the second capacitor is respectively connected to the first terminal of the sixth transistor and the low level voltage source, the first terminal of the seventh transistor is connected to the second terminal of the sixth transistor, and the gate of the seventh transistor is configured to input one of the M bits of the digital voltage signal.

6. The data driver of claim 5, wherein the second terminal of the seventh transistor is respectively connected to a common node, and a sum of currents flowing through the common node is the analog current signal.

7. A digital-voltage-to-analog-current converter for converting an M-bit digital voltage signal into an analog current signal in response to a first control signal and a second control signal, the converter comprising:

M first devices, responsive to the first control signal, configured to generate M first mirrored currents respectively; and

M second devices, responsive to the second control signal and the M first mirrored currents, configured to convert the digital voltage signal into the analog current signal.

8. The digital-voltage-to-analog-current converter of claim 7, wherein the converter further comprises:

a current source having at least M outputs for providing M different reference currents for the M first devices to generate the M first mirrored currents;

a high level voltage source; and

a low level voltage source.

9. The digital-voltage-to-analog-current converter of claim 8, wherein each of the M first devices comprises:

a first transistor, comprising a first terminal, a second terminal, and a gate;

a first capacitor, comprising a first end and a second end;

wherein the gate of the first transistor is configured to input the first control signal, the second terminal of the first transistor is connected to one of the M outputs, the first terminal of the first transistor is respectively connected to the first terminal of the second transistor and the second terminal of the third transistor, the gate of the second transistor is connected to the gate of the first transistor, the second terminal of the second transistor is respectively connected to the gate of the third transistor and the second end of the first capacitor, and the first end of the first capacitor is respectively connected to the first terminal of the third transistor and the high level voltage source.

10. The digital-voltage-to-analog-current converter of claim 9, wherein each of the M second devices comprises:

a fifth transistor, comprising a first terminal, a second terminal, and a gate;

a sixth transistor, comprising a first terminal, a second terminal, and a gate;

a second capacitor, comprising a first end and a second end;

wherein the gate of the fourth transistor is configured to input the second control signal, the second terminal of the fourth transistor is connected to the second terminal of the third transistor, the first terminal of the fourth transistor is respectively connected to the first terminal of the fifth transistor and the second terminal of the sixth transistor, the gate of the fifth transistor is connected to the gate of the fourth transistor, the second terminal of the fifth transistor is respectively connected to the gate of the sixth transistor and the second end of the second capacitor, the first end of the second capacitor is respectively connected to the first terminal of the sixth transistor and the low level voltage source, the first terminal of the seventh transistor is connected to the second terminal of the sixth transistor, and the gate of the seventh transistor is configured to input one of the M bits of the digital voltage signal.

11. The digital-voltage-to-analog-current converter of claim 10, wherein the second terminal of the seventh transistor is respectively connected to a common node, and a sum of currents flowing through the common node is the analog current signal.

12. A current mirror device, comprising:

a current source configured to provide a reference current;

a high level voltage source;

a low level voltage source;

a first control signal;

a second control signal;

a first transistor, comprising a first terminal, a second terminal, and a gate;

a third transistor, comprising a first terminal, a second terminal, and a gate;

a fifth transistor, comprising a first terminal, a second terminal, and a gate;

a sixth transistor, comprising a first terminal, a second terminal, and a gate;

a seventh transistor, comprising a first terminal, a second terminal, and a gate;

a first capacitor, comprising a first end and a second end; and

a second capacitor, comprising a first end and a second end;

wherein the gate of the first transistor is configured to input the first control signal, the second terminal of the first transistor is connected to the current source, the first terminal of the first transistor is respectively connected to the first terminal of the second transistor and the second terminal of the third transistor, the gate of the second transistor is connected to the gate of the first transistor, the second terminal of the second transistor is respectively connected to the gate of the third transistor and the second end of the first capacitor, the first end of the first capacitor is respectively connected to the first terminal of the third transistor and the high level voltage source, the gate of the fourth transistor is configured to input the second control signal, the second terminal of the fourth transistor is connected to the second terminal of the third transistor, the first terminal of the fourth transistor is respectively connected to the first terminal of the fifth transistor and the second terminal of the sixth transistor, the gate of the fifth transistor is connected to the gate of the fourth transistor, the second terminal of the fifth transistor is respectively connected to the gate of the sixth transistor and the second end of the second capacitor, the first end of the second capacitor is respectively connected to the first terminal of the sixth transistor and the low level voltage source, and a current flowing through the sixth transistor is substantially equal to the reference current.

13. The current mirror device of claim 12, wherein the first control signal is to enable or disable the first transistor and the second transistor, and when the first transistor and the second transistor are enabled, the reference current, flowing through the third transistor, is converted to a first voltage stored in the first capacitor.

14. The current mirror device of claim 13, wherein the second control signal is to enable or disable the fourth transistor and the fifth transistor, and when the fourth transistor and the fifth transistor are enabled, the first voltage, via the sixth transistor, is converted to a second voltage stored in the second capacitor.

15. The current mirror device of claim 14, wherein when the fourth transistor and the fifth transistor are disabled, the second voltage is converted to the current flowing through the sixth transistor.