US20110148681A1 - Digital-to-analog converter to produce paired control signals in a power supply controller - Google Patents
Digital-to-analog converter to produce paired control signals in a power supply controller Download PDFInfo
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- US20110148681A1 US20110148681A1 US12/642,450 US64245009A US2011148681A1 US 20110148681 A1 US20110148681 A1 US 20110148681A1 US 64245009 A US64245009 A US 64245009A US 2011148681 A1 US2011148681 A1 US 2011148681A1
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03M—CODING; DECODING; CODE CONVERSION IN GENERAL
- H03M1/00—Analogue/digital conversion; Digital/analogue conversion
- H03M1/66—Digital/analogue converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
- H02M3/33515—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with digital control
Definitions
- This invention is related to controllers for power supplies.
- the invention is related to controllers that control two parameters of a switching signal that controls a switch in a switching power supply.
- an ac-dc power supply receives an input that is between 100 and 240 volts rms (root mean square) from an ordinary ac electrical outlet. Switches in the power supply are switched on and off by a control circuit to provide a regulated output that may be suitable for providing current to light emitting diodes (LEDs) for illumination.
- the output is typically a regulated dc current, and the voltage at the LEDs is typically less than 40 volts.
- An ac-dc power supply that provides regulated current to LEDs typically must meet requirements for power factor and efficiency as explained below. Designers are challenged to provide satisfactory solutions at the lowest cost.
- the electrical outlet provides an ac voltage that has a waveform conforming to standards of magnitude, frequency, and harmonic content.
- the ac current drawn from the outlet is determined by the characteristics of the power supply that receives the ac voltage.
- regulatory agencies set standards for particular characteristics of the current that may be drawn from the ac electrical outlet. For example, a standard may set limits on the magnitudes of specific frequency components of the ac current. In another example, a standard may limit the rms value of the current in accordance with the amount of power that the outlet provides. Power in this context is the rate at which energy is consumed, typically measured in the units of watts.
- the general goal of all such standards for the ac current is to reduce the burden on the system that distributes ac power, sometimes called the power grid.
- Components of the current at frequencies other than the fundamental frequency of the ac voltage, sometimes called harmonic components, do no useful work, but yet the power grid must have the capacity to provide them and it must endure losses associated with them.
- Harmonic components generally distort the ideal current waveform so that it has a much higher maximum value than is necessary to deliver the required power. If the power grid does not have the capacity to provide the harmonic components, the waveform of the voltage will drop to an unacceptable value at times that are coincident with the peaks of the distorted waveform of the current.
- the most desirable ac current has a single frequency component that is at the fundamental frequency of the ac voltage.
- the waveform of the most desirable ac current will be in phase with the ac voltage. That is, the peak ac current will occur at the same time as the peak of the ac voltage.
- the ideal current will have an rms value that is equal to the value of the power from the outlet divided by the rms value of the voltage. In other words, the product of the rms voltage and the rms current will be equal to the power from the outlet when the current has ideal characteristics.
- Power factor is a measure of how closely the ac current approaches the ideal.
- the power factor is simply the power from the outlet divided by the product of the rms current multiplied by the rms voltage.
- a power factor of 100% is ideal.
- Currents that have frequency components other than the fundamental frequency of the ac voltage will yield a power factor less than 100% because such components increase the rms value but they do not contribute to the output power.
- Currents that have only the fundamental frequency of the ac voltage but are not in phase with the ac voltage will also yield a power factor less than 100% because the power from the outlet is reduced when the peak ac current does not occur at the same time as the peak ac voltage, while the rms value of the current remains at its ideal minimum value.
- the fundamental frequency of the ac voltage is typically either 50 Hz or 60 Hz in different regions of the world.
- the fundamental frequency of the ac voltage is nominally 60 Hz in North America and Taiwan, but it is 50 Hz in Europe and China.
- power supplies Since the power supply that receives the ac voltage determines the characteristics of the ac current, power supplies often use either special active circuits or special control techniques to maintain a high power factor. Power supplies that use only ordinary passive rectifier circuits at their inputs typically have low power factors that in some examples are less than 50%, whereas a power factor substantially greater than 90% is typically required to meet the standards for input current, such as for example the International Electrotechnical Commission (IEC) standard IED 61000-3-2. Although regulatory agencies in some regions may impose the standards, manufacturers of consumer equipment often voluntarily design their products to meet or to exceed standards for power factor to achieve a competitive advantage. Therefore, ac-dc power supplies for LEDs, for example, typically must include power factor correction.
- IEC International Electrotechnical Commission
- the efficiency of a power supply is a measure of how much of the power received by the power supply is delivered to the output of the power supply.
- a power supply that is 100% efficient delivers to the output all the power it receives at the input.
- a power supply that is for example 80% efficient delivers only 80% of the power it receives to the output, losing 20% of the power it receives.
- Regulatory agencies usually mandate minimum efficiencies for power supplies under various operating conditions.
- the efficiency of a power supply usually has a strong relationship to the switching frequency. Therefore, power supplies typically must control the switching frequency to maintain high efficiency.
- a power supply typically varies both the on-time and the frequency of a switching signal that switches a switch. As such, there is a need for an integrated circuit controller that can vary two control parameters in a precise and coordinated manner at low cost.
- FIG. 1 is a block diagram of one example of an ac-dc power supply that maintains a high power factor while regulating an output current at high efficiency, in accordance with the teachings of the present disclosure.
- FIG. 2 is functional block diagram of a digital-to-analog converter, in accordance with the teachings of the present disclosure.
- FIG. 3 is an example schematic diagram that shows a reference circuit, a current source, and a switch, in accordance with the teachings of the present disclosure.
- FIG. 4 is another example schematic diagram that shows a reference circuit, a current source, and a switch, in accordance with the teachings of the present disclosure.
- FIG. 1 shows the salient features of one example of an ac-dc power supply 100 receiving an ac input voltage V AC 102 that has a substantially sinusoidal waveform with a period T L that is the ac line period.
- the example power supply 100 of FIG. 1 has an ac input current I AC 104 .
- a full wave bridge rectifier 106 produces a dc rectified voltage V RECT 112 that is received by a dc-dc converter 116 .
- Rectified voltage V RECT 112 is positive with respect to an input return 108 .
- Dc-dc converter 106 has an input current I IN 114 that has a pulsating waveform with a period T S that is the switching period.
- the waveform of the pulsating input current I IN 114 has a triangular shape.
- the switching period T S is much less than the ac line period T L .
- the switching period T S is the reciprocal of the switching frequency
- the ac line period T L is the reciprocal of the ac line frequency.
- the switching period T S is about 15 microseconds whereas the ac line period T L is about 20 milliseconds.
- the ac line period T L is typically 1000 times greater than the switching period T S , so that there are typically 1000 switching periods within one ac line period.
- a small capacitor C 1 110 across the dc terminals of bridge rectifier 106 provides a low impedance source for the pulses of input current I IN 114 .
- Capacitor C 1 110 filters the high frequency components of input current I IN 114 such that the magnitude of the ac input current I AC 104 at any instant is substantially the average of the dc input current I IN 114 , the average taken over a switching period T S .
- Capacitor C 1 110 is small enough to allow the rectified voltage V RECT 112 to become substantially zero twice in every ac line period T L .
- Dc-dc converter 116 in the example of FIG. 1 is controlled by a controller 132 to regulate a substantially dc output current I O 124 that produces an output voltage V O 126 at a load 128 .
- Output voltage V O 126 is positive with respect to an output return 130 .
- load 128 is an arrangement of LEDs.
- the input return 108 is galvanically isolated from the output return 130 .
- Galvanic isolation prevents dc current from flowing between input and output of the power supply. In other words, a high dc voltage applied between an input terminal and an output terminal of a power supply with galvanic isolation will produce substantially no dc current between the input terminal and the output terminal of the power supply.
- Dc-dc converter 116 typically includes at least one switch 118 , at least one coupled inductor 120 , and at least one capacitor 122 .
- All standard converter configurations with pulsating input currents that are typically used to provide galvanically isolated outputs, such as for example the flyback converter and for example the many variants of the buck converter may be realized by an arrangement of switches, coupled inductors, and capacitors represented by the dc-dc converter block 116 in the example of FIG. 1 .
- a component such as switch 118 may still be considered an element of dc-dc converter 116 when switch 118 is physically located with circuits associated with a different function.
- switch 118 may be packaged together with bridge rectifier 106 , or switch 118 may be included with circuits of controller 132 in an integrated circuit that is manufactured as either a hybrid or a monolithic integrated circuit.
- controller 132 receives input current sense signal U IN 134 that is representative of the dc input current I IN 114 . Controller 132 also receives an output sense signal U OSENSE 136 that may be representative of the output current I O 124 , output voltage V O 126 , or a combination of the two. In other examples, controller 132 may receive a signal that is representative of the rectified voltage V RECT 112 in addition to the output sense signal U OSENSE 136 and the input current sense signal U IN 134 .
- Embodiments described in this disclosure may use many techniques to sense the input current I IN 114 as the current sense signal U IN 134 .
- the input current may be sensed as a voltage on a discrete resistor, or a current from a current transformer, or a voltage across the on-resistance of a metal oxide semiconductor field effect transistor (MOSFET) when the input current is the same as the current in the transistor, or as a current from the sense output of a current sensing field effect transistor (senseFET). Therefore, this disclosure will omit specific examples of techniques to sense dc input current I IN 114 .
- MOSFET metal oxide semiconductor field effect transistor
- a switch 118 included in dc-dc converter 116 is responsive to a switching signal (e.g., gate signal 158 ) received from controller 132 .
- gate signal 158 is a logic signal that may be high or low within a switching period T S .
- switch 118 is closed when gate signal 158 is high, and switch 118 is open when gate signal 158 is low.
- a closed switch is sometimes referred to as being in an on state.
- An open switch is sometimes referred to as being in an off state. In other words, a switch that turns on closes, and a switch that turns off opens.
- a switch in an on state may conduct current.
- a switch in an off state cannot conduct current.
- Switch 118 in the example of FIG. 1 is sometimes referred to as a single pole single throw (SPST) switch.
- An SPST switch has two terminals. The pole terminal is coupled to the signal to be switched.
- An SPST switch couples the pole terminal to the throw terminal when the switch is on.
- Switches of greater complexity may have multiple pole terminals and multiple throw terminals, with the number of throw terminals generally being equal to or greater than the number of pole terminals. It is appreciated that switches of greater complexity may be realized by multiple SPST switches.
- the dc input current I IN 114 is a pulsating current that is substantially zero when gate signal 158 is low.
- input current sense signal U IN 134 and output sense signal U OSENSE 136 may be any signals that have a known relationship to the dc input current I IN 114 and the output current I O 124 , or the output voltage V O 126 .
- voltage may be sensed as a current signal
- current may be sensed as a voltage signal.
- Controller 132 includes a response circuit 138 that includes analog and digital circuits that define the desired response of the gate signal 158 to input current sense signal U IN 134 and output sense signal U OSENSE 136 .
- the response circuit 138 may also include an oscillator (not shown) that provides timing signals such as for example a clock signal 140 that coordinates the operation of other circuits in the power supply, and also may provide other timing signals not shown in FIG. 1 (e.g., a maximum duty cycle signal).
- Controller 132 also includes a binary counter 146 , a digital-to-analog converter (DAC) 150 , and a variable oscillator 156 .
- Binary counter 146 produces logic signals B 0 through B n 148 that represent the binary digits (bits) of the number of events counted, where B 0 is the least significant bit (LSB) and B n is the most significant bit (MSB).
- binary counter 146 receives clock signal 140 , a count up signal 142 , and a count down signal 144 from response circuit 138 .
- every bit B X has a complement that is the logical inverse of B X available to circuits within controller 132 .
- binary counter 146 may produce logic signals B 0 through B n as well as their corresponding complementary logic signals B 0 through B n (not shown).
- controller 132 includes one or more inverters coupled to binary counter 146 to provide the complementary logic signals B 0 through B n in response to logic signals B 0 through B n respectively.
- binary counter 146 counts the number of low to high transitions of clock signal 140 .
- clock signal 140 increments the count of the counter.
- clock signal 140 decrements the count of the counter.
- DAC 150 converts the binary digits 148 from binary counter 146 into the paired analog signals U TON 152 and U TS 154 .
- the paired analog signals U TON 152 and U TS 154 may be voltages or currents.
- Analog signals U TON 152 and U TS 154 are restricted to have a fixed sum U MAX . In algebraic terms,
- Analog signals U TON 152 and U TS 154 are received by a variable oscillator 156 .
- Variable oscillator 156 produces a gate signal 158 that alternates between high and low values within switching period T S to switch the switch 118 in dc-dc converter 116 .
- Variable oscillator 156 responds to the magnitude of analog signal U TON 152 to set the duration T ON of the high value of gate signal 158 .
- Variable oscillator 156 responds to the magnitude of analog signal U TS 154 to set the period T S of gate signal 158 . Therefore, a single digital to analog converter (DAC 150 ) produces paired analog signals (U TON 152 and U TS 154 ) in a controller for a power supply.
- DAC 150 single digital to analog converter
- Variable oscillator 156 may process the paired analog signals U TON 152 and U TS 154 independently to produce desired combinations of T ON and T S that achieve the desired power factor, efficiency, and output performance of the power supply.
- U TON 152 and U TS 154 are currents.
- a current corresponding to U TON 152 may charge a capacitor to a fixed threshold voltage to determine the duration T ON .
- a current corresponding to U TS 154 may charge a capacitor in an oscillator to an upper fixed threshold voltage and discharge the capacitor to a lower fixed threshold voltage to determine the switching period T S .
- the time T ON would be inversely proportional to the magnitude of U TON 152 whereas the period T S would be inversely proportional to the magnitude of U TS 154 .
- the frequency f S is directly proportional to the magnitude of U TS .
- FIG. 2 shows an example of how the paired analog signals U TON 152 and U TS 154 may be produced as currents I TON and I TS respectively from a single DAC 150 that receives logic signals 148 that represent the binary digits from a binary counter 146 that produces an output of n+1 bits.
- Current sources 220 , 215 , 210 and 205 are coupled to a voltage source 280 , and the current sources have magnitudes that are weighted by powers of 2, with the lowest magnitude I B for current source 220 , magnitude twice I B for current source 215 , successively doubling the magnitude for each current source such the current source 205 with highest magnitude has magnitude 2 n I B for a counter with n+1 bits.
- the counter is an eight bit counter and thus the highest magnitude of current produced by a single current source may be 128 I B (i.e., 2 7 I B ).
- DAC 150 may optionally include a reference circuit (e.g., see reference circuit 305 of FIG. 3 ) coupled to each of the current sources 205 , 210 , 215 , and 220 to provide a reference for binary weighting of the currents produced.
- Single pole double throw (SPDT) switches 235 , 240 , 245 , and 250 coupled respectively to current sources 205 , 210 , 215 , and 220 are each switched by one of the binary digits 148 from binary counter 146 .
- SPDT switch is equivalent to two SPST switches that are coupled at their pole terminals, one switch is on when the other switch is off.
- a high value for one of the digits couples its respective current source to the node 270 such that all the current from the current source contributes to the current I TS of the analog signal 154 .
- a low value for one of the digits (which is a high value for the complement of the digit) couples its respective current source to the node 265 such that all the current from the current source contributes to the current I TON of the analog signal 152 .
- a high value for binary bit B 1 switches SPDT switch 245 to a first position such that the current 2 I B from current source 215 is switched to node 255 , contributing to analog signal 154 .
- a low value for binary bit B 1 switches SPDT switch 245 to a second position such that the current 2 I B from current 215 is switched to node 260 , contributing to analog signal 152 .
- a current proportional to that number contributes to analog signal 154
- a current proportional to the complement of that binary number contributes to analog signal 152 .
- DAC 150 also includes a current source 225 that sets a minimum current I MINTON for analog signal 152 , and a current source 230 that sets a minimum current I MINTS for analog signal 154 .
- Table 1 illustrates an example relationship between logic signals B 0 through B 3 , I TON and I TS .
- Table 1 illustrates the logic signals as including 4 bits, any number of bits may be utilized including 1 or more, in accordance with the teachings of the present disclosure.
- Table 1 illustrates that as the count represented by logic signals B 0 through B 3 increases, so too does the magnitude of the current contributing to analog signal I TS 154 .
- Table 1 further illustrates that as the count increases, the magnitude of the current contributing to analog signal I TON 152 decreases. However, as stated above, the sum of the analog signals 152 and 154 is a fixed value.
- the sum of I TON +I TS remains substantially constant for all values of the binary digits that that are received by DAC 150 .
- FIG. 3 is an example schematic diagram that shows a reference circuit 305 , a current source 385 , and an SPDT switch 380 , in accordance with the teachings of the present disclosure.
- Current source 375 is one possible implementation of current source 215 of FIG. 2 .
- SPDT switch 380 is one possible implementation of switch 245 of FIG. 2 .
- FIG. 3 further shows a reference circuit 305 that is not shown in FIG. 2 , but may be included in DAC 150 .
- reference circuit 305 couples to each binary-weighted current source of FIG. 2 . All SPDT switches included in DAC 150 may be identical to SPDT switch 380 .
- reference circuit 305 includes p-channel MOSFETs 310 , 315 , 320 , 330 and 335 .
- Transistors 310 and 315 mirror the current I REF1 from a first current source 325 into the source terminal of transistor 320 to establish a reference voltage on node 375 .
- the reference voltage on node 375 is selected to guarantee operation of current source 385 under all anticipated conditions.
- I REF1 is approximately 1 microampere.
- a second current source 340 sets the current I REF2 in transistors 330 and 335 .
- I REF2 is approximately 2 microamperes.
- Transistors 330 and 335 are coupled in a typical p-channel cascode arrangement that is duplicated in the arrangement of transistors 345 and 350 to form current source 215 and the other binary-weighted current sources in DAC 150 .
- the physical dimensions of transistors 345 and 350 may be scaled with respect to transistors 330 and 335 so that the current from current source 385 is the desired multiple of current I REF2 from the second current source 340 .
- the scaling of transistors 345 and 350 may include selecting the length and width of channel regions to provide desired ratios of the drain currents.
- the physical dimensions of transistors 345 and 350 are scaled such that current source 385 provides a current substantially equal to 2 I B . Further scaling of the physical dimensions of transistors included in the remaining current sources of DAC 150 may be implemented to achieve the desired binary weighting of each current source as shown in FIG. 2 .
- FIG. 4 is an example schematic diagram that shows reference circuit 305 , a current source 405 , and SPDT switch 380 , in accordance with the teachings of the present disclosure.
- Current source 405 is one possible implementation of current source 215 of FIG. 2 .
- the physical dimensions of transistor 330 are substantially the same as the dimensions of transistor 410 and also of transistor 415 .
- each current source of DAC 150 may include multiple transistors of fixed dimensions coupled in parallel to provide the binary weighting shown in FIG. 2 .
- p-channel MOSFETs 355 and 360 form SPDT switch 380 .
- binary bit B 1 from binary counter 146 is coupled to the gate 370 of p-channel transistor 360 .
- the complement of binary bit B 1 from binary counter 146 is coupled to the gate 365 of p-channel transistor 355 .
- binary bit B 1 at the gate 370 of transistor 360 is high to turn transistor 360 off, the complement to binary bit B 1 at the gate 365 of transistor 355 is low to turn transistor 355 on.
- power supply controller 132 The functions of power supply controller 132 are typically realized in an integrated circuit. Therefore, use of a single digital-to-analog converter to provide two control signals in contrast to the use of two digital-to-analog converters to provide the same two control signals reduces the cost of an integrated circuit controller for a power supply.
Abstract
Description
- 1. Field of the Disclosure
- This invention is related to controllers for power supplies. In particular, the invention is related to controllers that control two parameters of a switching signal that controls a switch in a switching power supply.
- 2. Background
- In a typical application, an ac-dc power supply receives an input that is between 100 and 240 volts rms (root mean square) from an ordinary ac electrical outlet. Switches in the power supply are switched on and off by a control circuit to provide a regulated output that may be suitable for providing current to light emitting diodes (LEDs) for illumination. The output is typically a regulated dc current, and the voltage at the LEDs is typically less than 40 volts.
- An ac-dc power supply that provides regulated current to LEDs typically must meet requirements for power factor and efficiency as explained below. Designers are challenged to provide satisfactory solutions at the lowest cost.
- The electrical outlet provides an ac voltage that has a waveform conforming to standards of magnitude, frequency, and harmonic content. The ac current drawn from the outlet, however, is determined by the characteristics of the power supply that receives the ac voltage. In many applications, regulatory agencies set standards for particular characteristics of the current that may be drawn from the ac electrical outlet. For example, a standard may set limits on the magnitudes of specific frequency components of the ac current. In another example, a standard may limit the rms value of the current in accordance with the amount of power that the outlet provides. Power in this context is the rate at which energy is consumed, typically measured in the units of watts.
- The general goal of all such standards for the ac current is to reduce the burden on the system that distributes ac power, sometimes called the power grid. Components of the current at frequencies other than the fundamental frequency of the ac voltage, sometimes called harmonic components, do no useful work, but yet the power grid must have the capacity to provide them and it must endure losses associated with them. Harmonic components generally distort the ideal current waveform so that it has a much higher maximum value than is necessary to deliver the required power. If the power grid does not have the capacity to provide the harmonic components, the waveform of the voltage will drop to an unacceptable value at times that are coincident with the peaks of the distorted waveform of the current. The most desirable ac current has a single frequency component that is at the fundamental frequency of the ac voltage. Moreover, the waveform of the most desirable ac current will be in phase with the ac voltage. That is, the peak ac current will occur at the same time as the peak of the ac voltage. The ideal current will have an rms value that is equal to the value of the power from the outlet divided by the rms value of the voltage. In other words, the product of the rms voltage and the rms current will be equal to the power from the outlet when the current has ideal characteristics.
- Power factor is a measure of how closely the ac current approaches the ideal. The power factor is simply the power from the outlet divided by the product of the rms current multiplied by the rms voltage. A power factor of 100% is ideal. Currents that have frequency components other than the fundamental frequency of the ac voltage will yield a power factor less than 100% because such components increase the rms value but they do not contribute to the output power. Currents that have only the fundamental frequency of the ac voltage but are not in phase with the ac voltage will also yield a power factor less than 100% because the power from the outlet is reduced when the peak ac current does not occur at the same time as the peak ac voltage, while the rms value of the current remains at its ideal minimum value. That is, an ideal ac current that is not in phase with the ac voltage will yield a power factor less than 100%. The fundamental frequency of the ac voltage is typically either 50 Hz or 60 Hz in different regions of the world. By way of example, the fundamental frequency of the ac voltage is nominally 60 Hz in North America and Taiwan, but it is 50 Hz in Europe and China.
- Since the power supply that receives the ac voltage determines the characteristics of the ac current, power supplies often use either special active circuits or special control techniques to maintain a high power factor. Power supplies that use only ordinary passive rectifier circuits at their inputs typically have low power factors that in some examples are less than 50%, whereas a power factor substantially greater than 90% is typically required to meet the standards for input current, such as for example the International Electrotechnical Commission (IEC) standard IED 61000-3-2. Although regulatory agencies in some regions may impose the standards, manufacturers of consumer equipment often voluntarily design their products to meet or to exceed standards for power factor to achieve a competitive advantage. Therefore, ac-dc power supplies for LEDs, for example, typically must include power factor correction.
- The efficiency of a power supply is a measure of how much of the power received by the power supply is delivered to the output of the power supply. A power supply that is 100% efficient delivers to the output all the power it receives at the input. A power supply that is for example 80% efficient delivers only 80% of the power it receives to the output, losing 20% of the power it receives. Regulatory agencies usually mandate minimum efficiencies for power supplies under various operating conditions. The efficiency of a power supply usually has a strong relationship to the switching frequency. Therefore, power supplies typically must control the switching frequency to maintain high efficiency.
- To provide a regulated output current at high efficiency from a power factor corrected ac input, a power supply typically varies both the on-time and the frequency of a switching signal that switches a switch. As such, there is a need for an integrated circuit controller that can vary two control parameters in a precise and coordinated manner at low cost.
- Non-limiting and non-exhaustive embodiments of the present invention are described with reference to the following figures, wherein like reference numerals refer to like parts throughout the various views unless otherwise specified.
-
FIG. 1 is a block diagram of one example of an ac-dc power supply that maintains a high power factor while regulating an output current at high efficiency, in accordance with the teachings of the present disclosure. -
FIG. 2 is functional block diagram of a digital-to-analog converter, in accordance with the teachings of the present disclosure. -
FIG. 3 is an example schematic diagram that shows a reference circuit, a current source, and a switch, in accordance with the teachings of the present disclosure. -
FIG. 4 is another example schematic diagram that shows a reference circuit, a current source, and a switch, in accordance with the teachings of the present disclosure. - Methods and apparatuses for implementing a digital-to-analog converter to produce paired control signals in a power supply controller are disclosed. In the following description, numerous specific details are set forth in order to provide a thorough understanding of the present invention. It will be apparent, however, to one having ordinary skill in the art that the specific detail need not be employed to practice the present invention. In other instances, well-known materials or methods have not been described in detail in order to avoid obscuring the present invention.
- Reference throughout this specification to “one embodiment”, “an embodiment”, “one example” or “an example” means that a particular feature, structure or characteristic described in connection with the embodiment or example is included in at least one embodiment of the present invention. Thus, appearances of the phrases “in one embodiment”, “in an embodiment”, “one example” or “an example” in various places throughout this specification are not necessarily all referring to the same embodiment or example. Furthermore, the particular features, structures or characteristics may be combined in any suitable combinations and/or subcombinations in one or more embodiments or examples. Particular features, structures or characteristics may be included in an integrated circuit, an electronic circuit, a combinational logic circuit, or other suitable components that provide the described functionality. In addition, it is appreciated that the figures provided herewith are for explanation purposes to persons ordinarily skilled in the art and that the drawings are not necessarily drawn to scale.
- The schematic diagram of
FIG. 1 shows the salient features of one example of an ac-dc power supply 100 receiving an acinput voltage V AC 102 that has a substantially sinusoidal waveform with a period TL that is the ac line period. Theexample power supply 100 ofFIG. 1 has an ac input current IAC 104. - In the example power supply of
FIG. 1 , a fullwave bridge rectifier 106 produces a dc rectifiedvoltage V RECT 112 that is received by a dc-dc converter 116. Rectifiedvoltage V RECT 112 is positive with respect to aninput return 108. Dc-dc converter 106 has an input current IIN 114 that has a pulsating waveform with a period TS that is the switching period. In the example ofFIG. 1 , the waveform of the pulsating input current IIN 114 has a triangular shape. The switching period TS is much less than the ac line period TL. The switching period TS is the reciprocal of the switching frequency, and the ac line period TL is the reciprocal of the ac line frequency. In one example, the switching period TS is about 15 microseconds whereas the ac line period TL is about 20 milliseconds. In other words, the ac line period TL is typically 1000 times greater than the switching period TS, so that there are typically 1000 switching periods within one ac line period. - In the example power supply of
FIG. 1 , asmall capacitor C1 110 across the dc terminals ofbridge rectifier 106 provides a low impedance source for the pulses of inputcurrent I IN 114.Capacitor C1 110 filters the high frequency components of input current IIN 114 such that the magnitude of the ac input current IAC 104 at any instant is substantially the average of the dc input current IIN 114, the average taken over a switching period TS. Capacitor C1 110 is small enough to allow the rectifiedvoltage V RECT 112 to become substantially zero twice in every ac line period TL. - Dc-
dc converter 116 in the example ofFIG. 1 is controlled by acontroller 132 to regulate a substantially dc output current IO 124 that produces anoutput voltage V O 126 at aload 128.Output voltage V O 126 is positive with respect to anoutput return 130. In one example, load 128 is an arrangement of LEDs. - In the example of
FIG. 1 , theinput return 108 is galvanically isolated from theoutput return 130. Galvanic isolation prevents dc current from flowing between input and output of the power supply. In other words, a high dc voltage applied between an input terminal and an output terminal of a power supply with galvanic isolation will produce substantially no dc current between the input terminal and the output terminal of the power supply. - Dc-
dc converter 116 typically includes at least oneswitch 118, at least one coupledinductor 120, and at least onecapacitor 122. All standard converter configurations with pulsating input currents that are typically used to provide galvanically isolated outputs, such as for example the flyback converter and for example the many variants of the buck converter may be realized by an arrangement of switches, coupled inductors, and capacitors represented by the dc-dc converter block 116 in the example ofFIG. 1 . - The various components identified with the functions of the dc-
dc converter 116 and thecontroller 132 need not be confined to the boundaries suggested by the boxes drawn in theexample power supply 100 ofFIG. 1 . The individual components are segregated into easily identifiable regions in this disclosure to aid the explanation of the invention. Therefore, for example, a component such asswitch 118 may still be considered an element of dc-dc converter 116 whenswitch 118 is physically located with circuits associated with a different function. For example, switch 118 may be packaged together withbridge rectifier 106, or switch 118 may be included with circuits ofcontroller 132 in an integrated circuit that is manufactured as either a hybrid or a monolithic integrated circuit. - In the example of
FIG. 1 ,controller 132 receives input currentsense signal U IN 134 that is representative of the dc inputcurrent I IN 114.Controller 132 also receives an outputsense signal U OSENSE 136 that may be representative of the output current IO 124,output voltage V O 126, or a combination of the two. In other examples,controller 132 may receive a signal that is representative of the rectifiedvoltage V RECT 112 in addition to the outputsense signal U OSENSE 136 and the input currentsense signal U IN 134. - Embodiments described in this disclosure may use many techniques to sense the input current IIN 114 as the current
sense signal U IN 134. For example, the input current may be sensed as a voltage on a discrete resistor, or a current from a current transformer, or a voltage across the on-resistance of a metal oxide semiconductor field effect transistor (MOSFET) when the input current is the same as the current in the transistor, or as a current from the sense output of a current sensing field effect transistor (senseFET). Therefore, this disclosure will omit specific examples of techniques to sense dc inputcurrent I IN 114. - In the example of
FIG. 1 , aswitch 118 included in dc-dc converter 116 is responsive to a switching signal (e.g., gate signal 158) received fromcontroller 132. In the example ofFIG. 1 ,gate signal 158 is a logic signal that may be high or low within a switching period TS. In one example, switch 118 is closed whengate signal 158 is high, and switch 118 is open whengate signal 158 is low. A closed switch is sometimes referred to as being in an on state. An open switch is sometimes referred to as being in an off state. In other words, a switch that turns on closes, and a switch that turns off opens. A switch in an on state may conduct current. A switch in an off state cannot conduct current.Switch 118 in the example ofFIG. 1 is sometimes referred to as a single pole single throw (SPST) switch. An SPST switch has two terminals. The pole terminal is coupled to the signal to be switched. An SPST switch couples the pole terminal to the throw terminal when the switch is on. Switches of greater complexity may have multiple pole terminals and multiple throw terminals, with the number of throw terminals generally being equal to or greater than the number of pole terminals. It is appreciated that switches of greater complexity may be realized by multiple SPST switches. In the example ofFIG. 1 , the dc input current IIN 114 is a pulsating current that is substantially zero whengate signal 158 is low. - It is appreciated that input current
sense signal U IN 134 and outputsense signal U OSENSE 136 may be any signals that have a known relationship to the dc input current IIN 114 and the output current IO 124, or theoutput voltage V O 126. In other words, voltage may be sensed as a current signal, and current may be sensed as a voltage signal. -
Controller 132 includes aresponse circuit 138 that includes analog and digital circuits that define the desired response of thegate signal 158 to input currentsense signal U IN 134 and outputsense signal U OSENSE 136. Theresponse circuit 138 may also include an oscillator (not shown) that provides timing signals such as for example aclock signal 140 that coordinates the operation of other circuits in the power supply, and also may provide other timing signals not shown inFIG. 1 (e.g., a maximum duty cycle signal). -
Controller 132 also includes abinary counter 146, a digital-to-analog converter (DAC) 150, and avariable oscillator 156.Binary counter 146 produces logic signals B0 through Bn 148 that represent the binary digits (bits) of the number of events counted, where B0 is the least significant bit (LSB) and Bn is the most significant bit (MSB). In the example ofFIG. 1 ,binary counter 146 receivesclock signal 140, a count upsignal 142, and a count down signal 144 fromresponse circuit 138. In one example,binary counter 146 is an eight bit counter (i.e., n=7). It is understood that every bit BX has a complement that is the logical inverse of BX available to circuits withincontroller 132. For example,binary counter 146 may produce logic signals B0 through Bn as well as their corresponding complementary logic signalsB0 throughBn (not shown). In another example,controller 132 includes one or more inverters coupled tobinary counter 146 to provide the complementary logic signalsB0 throughBn in response to logic signals B0 through Bn respectively. - In the example of
FIG. 1 ,binary counter 146 counts the number of low to high transitions ofclock signal 140. When the count upsignal 142 is asserted in the example ofFIG. 1 ,clock signal 140 increments the count of the counter. When the count downsignal 140 is asserted in the example ofFIG. 1 ,clock signal 140 decrements the count of the counter. - In the example of
FIG. 1 ,DAC 150 converts the binary digits 148 frombinary counter 146 into the pairedanalog signals U TON 152 andU TS 154. The pairedanalog signals U TON 152 andU TS 154 may be voltages or currents. Analog signalsU TON 152 andU TS 154 are restricted to have a fixed sum UMAX. In algebraic terms, -
U TON +U TS =U MAX (EQ. 1) - Analog signals
U TON 152 andU TS 154 are received by avariable oscillator 156.Variable oscillator 156 produces agate signal 158 that alternates between high and low values within switching period TS to switch theswitch 118 in dc-dc converter 116. -
Variable oscillator 156 responds to the magnitude ofanalog signal U TON 152 to set the duration TON of the high value ofgate signal 158.Variable oscillator 156 responds to the magnitude ofanalog signal U TS 154 to set the period TS ofgate signal 158. Therefore, a single digital to analog converter (DAC 150) produces paired analog signals (U TON 152 and UTS 154) in a controller for a power supply. -
Variable oscillator 156 may process the pairedanalog signals U TON 152 andU TS 154 independently to produce desired combinations of TON and TS that achieve the desired power factor, efficiency, and output performance of the power supply. In one example,U TON 152 andU TS 154 are currents. In one example, a current corresponding toU TON 152 may charge a capacitor to a fixed threshold voltage to determine the duration TON. In one example, a current corresponding toU TS 154 may charge a capacitor in an oscillator to an upper fixed threshold voltage and discharge the capacitor to a lower fixed threshold voltage to determine the switching period TS. Thus, in one example the time TON would be inversely proportional to the magnitude ofU TON 152 whereas the period TS would be inversely proportional to the magnitude ofU TS 154. When the period TS is inversely proportional to the magnitude of UTS, the frequency fS is directly proportional to the magnitude of UTS. -
FIG. 2 shows an example of how the pairedanalog signals U TON 152 andU TS 154 may be produced as currents ITON and ITS respectively from asingle DAC 150 that receives logic signals 148 that represent the binary digits from abinary counter 146 that produces an output of n+1 bits.Current sources voltage source 280, and the current sources have magnitudes that are weighted by powers of 2, with the lowest magnitude IB forcurrent source 220, magnitude twice IB forcurrent source 215, successively doubling the magnitude for each current source such thecurrent source 205 with highest magnitude has magnitude 2 nIB for a counter with n+1 bits. In one example, the counter is an eight bit counter and thus the highest magnitude of current produced by a single current source may be 128IB (i.e., 2 7IB).DAC 150 may optionally include a reference circuit (e.g., seereference circuit 305 ofFIG. 3 ) coupled to each of thecurrent sources - Single pole double throw (SPDT) switches 235, 240, 245, and 250 coupled respectively to
current sources binary counter 146. It is appreciated that an SPDT switch is equivalent to two SPST switches that are coupled at their pole terminals, one switch is on when the other switch is off. In the example ofFIG. 2 , a high value for one of the digits couples its respective current source to thenode 270 such that all the current from the current source contributes to the current ITS of theanalog signal 154. Conversely, a low value for one of the digits, (which is a high value for the complement of the digit) couples its respective current source to thenode 265 such that all the current from the current source contributes to the current ITON of theanalog signal 152. - For example, a high value for binary bit B1 switches
SPDT switch 245 to a first position such that the current 2IB fromcurrent source 215 is switched tonode 255, contributing toanalog signal 154. Conversely, a low value for binary bit B1 switchesSPDT switch 245 to a second position such that the current 2IB from current 215 is switched tonode 260, contributing toanalog signal 152. Thus, for every number frombinary counter 146, a current proportional to that number contributes toanalog signal 154, while a current proportional to the complement of that binary number contributes toanalog signal 152. - In the example of
FIG. 2 ,DAC 150 also includes acurrent source 225 that sets a minimum current IMINTON foranalog signal 152, and acurrent source 230 that sets a minimum current IMINTS foranalog signal 154. -
TABLE 1 B3 B2 B1 B0 ITON ITS ITON + ITS 0 0 0 0 IMINTON + 15IB IMINTS IMINTON + IMINTS + 15IB 0 0 0 1 IMINTON + 14IB IMINTS + IB IMINTON + IMINTS + 15IB 0 0 1 0 IMINTON + 13IB IMINTS + 2IB IMINTON + IMINTS + 15IB 0 0 1 1 IMINTON + 12IB IMINTS + 3IB IMINTON + IMINTS + 15IB 0 1 0 0 IMINTON + 11IB IMINTS + 4IB IMINTON + IMINTS + 15IB 0 1 0 1 IMINTON + 10IB IMINTS + 5IB IMINTON + IMINTS + 15IB 0 1 1 0 IMINTON + 9IB IMINTS + 6IB IMINTON + IMINTS + 15IB 0 1 1 1 IMINTON + 8IB IMINTS + 7IB IMINTON + IMINTS + 15I B1 0 0 0 IMINTON + 7IB IMINTS + 8IB IMINTON + IMINTS + 15I B1 0 0 1 IMINTON + 6IB IMINTS + 9IB IMINTON + IMINTS + 15I B1 0 1 0 IMINTON + 5IB IMINTS + 10IB IMINTON + IMINTS + 15I B1 0 1 1 IMINTON + 4IB IMINTS + 11IB IMINTON + IMINTS + 15I B1 1 0 0 IMINTON + 3IB IMINTS + 12IB IMINTON + IMINTS + 15I B1 1 0 1 IMINTON + 2IB IMINTS + 13B IMINTON + IMINTS + 15I B1 1 1 0 IMINTON + 1IB IMINTS + 14IB IMINTON + IMINTS + 15I B1 1 1 1 IMINTON IMINTS + 15IB IMINTON + IMINTS + 15IB - Table 1 illustrates an example relationship between logic signals B0 through B3, ITON and ITS. Although Table 1 illustrates the logic signals as including 4 bits, any number of bits may be utilized including 1 or more, in accordance with the teachings of the present disclosure. As shown in Table 1, as the count represented by logic signals B0 through B3 increases, so too does the magnitude of the current contributing to
analog signal I TS 154. Table 1 further illustrates that as the count increases, the magnitude of the current contributing to analog signal ITON 152 decreases. However, as stated above, the sum of the analog signals 152 and 154 is a fixed value. Thus, as shown in Table 1, the sum of ITON+ITS remains substantially constant for all values of the binary digits that that are received byDAC 150. -
FIG. 3 is an example schematic diagram that shows areference circuit 305, acurrent source 385, and anSPDT switch 380, in accordance with the teachings of the present disclosure.Current source 375 is one possible implementation ofcurrent source 215 ofFIG. 2 .SPDT switch 380 is one possible implementation ofswitch 245 ofFIG. 2 .FIG. 3 further shows areference circuit 305 that is not shown inFIG. 2 , but may be included inDAC 150. In oneexample reference circuit 305 couples to each binary-weighted current source ofFIG. 2 . All SPDT switches included inDAC 150 may be identical toSPDT switch 380. - In the example of
FIG. 3 ,reference circuit 305 includes p-channel MOSFETs Transistors current source 325 into the source terminal oftransistor 320 to establish a reference voltage onnode 375. The reference voltage onnode 375 is selected to guarantee operation ofcurrent source 385 under all anticipated conditions. In one example, IREF1 is approximately 1 microampere. A secondcurrent source 340 sets the current IREF2 intransistors Transistors transistors current source 215 and the other binary-weighted current sources inDAC 150. - The physical dimensions of
transistors transistors current source 385 is the desired multiple of current IREF2 from the secondcurrent source 340. The scaling oftransistors transistors current source 385 provides a current substantially equal to 2IB. Further scaling of the physical dimensions of transistors included in the remaining current sources ofDAC 150 may be implemented to achieve the desired binary weighting of each current source as shown inFIG. 2 . - The scaling of
transistors transistors FIG. 4 is an example schematic diagram that showsreference circuit 305, acurrent source 405, andSPDT switch 380, in accordance with the teachings of the present disclosure.Current source 405 is one possible implementation ofcurrent source 215 ofFIG. 2 . In the examplecurrent source 405 ofFIG. 4 , the physical dimensions oftransistor 330 are substantially the same as the dimensions oftransistor 410 and also oftransistor 415. Similarly, the physical dimensions oftransistor 335 are substantially the same as the dimensions oftransistors transistors transistors 415 and 425 (i.e., the respective gates oftransistors transistors transistors transistors current source 405 is scaled to substantially 2IB. Thus, each current source ofDAC 150 may include multiple transistors of fixed dimensions coupled in parallel to provide the binary weighting shown inFIG. 2 . - Referring now to the examples of both
FIGS. 3 and 4 , p-channel MOSFETs form SPDT switch 380. In theSPDT switch 245 ofFIG. 2 , binary bit B1 frombinary counter 146 is coupled to thegate 370 of p-channel transistor 360. In theSPDT switch 245 ofFIG. 2 , the complement of binary bit B1 frombinary counter 146 is coupled to thegate 365 of p-channel transistor 355. When binary bit B1 at thegate 370 oftransistor 360 is high to turntransistor 360 off, the complement to binary bit B1 at thegate 365 oftransistor 355 is low to turntransistor 355 on. When binary bit B1 at thegate 370 oftransistor 360 is low to turntransistor 360 on, the complement to binary bit B1 at thegate 365 oftransistor 355 is high to turntransistor 355 off. Thus, when binary bit B1 is high the current fromcurrent source 215 is directed tonode 255, and when binary bit B1 is low the current fromcurrent source 215 is directed tonode 260. - The functions of
power supply controller 132 are typically realized in an integrated circuit. Therefore, use of a single digital-to-analog converter to provide two control signals in contrast to the use of two digital-to-analog converters to provide the same two control signals reduces the cost of an integrated circuit controller for a power supply. - The above description of illustrated examples of the present invention, including what is described in the Abstract, are not intended to be exhaustive or to be limitation to the precise forms disclosed. While specific embodiments of, and examples for, the invention are described herein for illustrative purposes, various equivalent modifications are possible without departing from the broader spirit and scope of the present invention. Indeed, it is appreciated that the specific voltages, currents, frequencies, power range values, times, etc., are provided for explanation purposes and that other values may also be employed in other embodiments and examples in accordance with the teachings of the present invention.
- These modifications can be made to examples of the invention in light of the above detailed description. The terms used in the following claims should not be construed to limit the invention to the specific embodiments disclosed in the specification and the claims. Rather, the scope is to be determined entirely by the following claims, which are to be construed in accordance with established doctrines of claim interpretation. The present specification and figures are accordingly to be regarded as illustrative rather than restrictive.
Claims (19)
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US12/642,450 US7978107B1 (en) | 2009-12-18 | 2009-12-18 | Digital-to-analog converter to produce paired control signals in a power supply controller |
US13/117,998 US8599052B2 (en) | 2009-12-18 | 2011-05-27 | Digital-to-analog converter to produce paired control signals in a power supply controller |
US14/067,696 US20140055293A1 (en) | 2009-12-18 | 2013-10-30 | Digital-to-analog converter to produce paired control signals in a power supply controller |
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US13/117,998 Expired - Fee Related US8599052B2 (en) | 2009-12-18 | 2011-05-27 | Digital-to-analog converter to produce paired control signals in a power supply controller |
US14/067,696 Abandoned US20140055293A1 (en) | 2009-12-18 | 2013-10-30 | Digital-to-analog converter to produce paired control signals in a power supply controller |
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Cited By (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US8867245B1 (en) * | 2010-09-27 | 2014-10-21 | Champion Microelectronic Corporation | Switching power supply having high-power integrated circuit and monolithic integrated circuit therefor |
CN105099147A (en) * | 2014-05-13 | 2015-11-25 | 电力集成公司 | Multi-pace controller |
US20170194947A1 (en) * | 2016-01-05 | 2017-07-06 | Mediatek Singapore Pte. Ltd. | Signal self-calibration circuits and methods |
US20180081386A1 (en) * | 2016-09-21 | 2018-03-22 | Infineon Technologies Austria Ag | Dac controlled low power high output current source |
Families Citing this family (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP5161944B2 (en) * | 2010-09-21 | 2013-03-13 | 株式会社東芝 | Digital-analog converter and wireless communication device |
US9203424B1 (en) * | 2014-05-13 | 2015-12-01 | Power Integrations, Inc. | Digital-to-analog converter circuit for use in a power converter |
EP3987890A4 (en) * | 2019-06-21 | 2022-07-06 | Texas Instruments Incorporated | Dynamic driver voltage headroom adjustment |
Citations (7)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US4638417A (en) * | 1985-08-16 | 1987-01-20 | Sperry Corporation | Power density spectrum controller |
US5198785A (en) * | 1992-05-29 | 1993-03-30 | Analog Devices, Inc. | Dual edge pulse width modulation system |
US5208559A (en) * | 1992-05-29 | 1993-05-04 | Analog Devices, Inc. | Pulse shaping system for a pulse width modulation system |
US5563605A (en) * | 1995-08-02 | 1996-10-08 | The Regents Of The University Of California | Precision digital pulse phase generator |
US20020021236A1 (en) * | 1999-08-25 | 2002-02-21 | Pivotal Technologies Corp. | CMOS DAC with high impedance differential current drivers |
US6501402B2 (en) * | 2001-05-09 | 2002-12-31 | Broadcom Corporation | Digital-to-analogue converter using an array of current sources |
US7548047B1 (en) * | 2005-05-03 | 2009-06-16 | Marvell International Ltd. | Pulse width modulated buck voltage regulator with stable feedback control loop |
Family Cites Families (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US7362191B2 (en) * | 2004-04-29 | 2008-04-22 | Linear Technology Corporation | Methods and circuits for frequency modulation that reduce the spectral noise of switching regulators |
-
2009
- 2009-12-18 US US12/642,450 patent/US7978107B1/en active Active
-
2011
- 2011-05-27 US US13/117,998 patent/US8599052B2/en not_active Expired - Fee Related
-
2013
- 2013-10-30 US US14/067,696 patent/US20140055293A1/en not_active Abandoned
Patent Citations (7)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US4638417A (en) * | 1985-08-16 | 1987-01-20 | Sperry Corporation | Power density spectrum controller |
US5198785A (en) * | 1992-05-29 | 1993-03-30 | Analog Devices, Inc. | Dual edge pulse width modulation system |
US5208559A (en) * | 1992-05-29 | 1993-05-04 | Analog Devices, Inc. | Pulse shaping system for a pulse width modulation system |
US5563605A (en) * | 1995-08-02 | 1996-10-08 | The Regents Of The University Of California | Precision digital pulse phase generator |
US20020021236A1 (en) * | 1999-08-25 | 2002-02-21 | Pivotal Technologies Corp. | CMOS DAC with high impedance differential current drivers |
US6501402B2 (en) * | 2001-05-09 | 2002-12-31 | Broadcom Corporation | Digital-to-analogue converter using an array of current sources |
US7548047B1 (en) * | 2005-05-03 | 2009-06-16 | Marvell International Ltd. | Pulse width modulated buck voltage regulator with stable feedback control loop |
Cited By (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US8867245B1 (en) * | 2010-09-27 | 2014-10-21 | Champion Microelectronic Corporation | Switching power supply having high-power integrated circuit and monolithic integrated circuit therefor |
CN105099147A (en) * | 2014-05-13 | 2015-11-25 | 电力集成公司 | Multi-pace controller |
US20170194947A1 (en) * | 2016-01-05 | 2017-07-06 | Mediatek Singapore Pte. Ltd. | Signal self-calibration circuits and methods |
US20180081386A1 (en) * | 2016-09-21 | 2018-03-22 | Infineon Technologies Austria Ag | Dac controlled low power high output current source |
US10061341B2 (en) * | 2016-09-21 | 2018-08-28 | Infineon Technologies Austria Ag | DAC controlled low power high output current source |
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US20140055293A1 (en) | 2014-02-27 |
US7978107B1 (en) | 2011-07-12 |
US8599052B2 (en) | 2013-12-03 |
US20110228567A1 (en) | 2011-09-22 |
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