US8040965B2 - Method and apparatus for processing data for transmission in a multi-channel communication system using selective channel inversion - Google Patents
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- H04B—TRANSMISSION
- H04B7/00—Radio transmission systems, i.e. using radiation field
- H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
- H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
- H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
- H04B7/0686—Hybrid systems, i.e. switching and simultaneous transmission
- H04B7/0689—Hybrid systems, i.e. switching and simultaneous transmission using different transmission schemes, at least one of them being a diversity transmission scheme
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B7/00—Radio transmission systems, i.e. using radiation field
- H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
- H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
- H04B7/0413—MIMO systems
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- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L1/00—Arrangements for detecting or preventing errors in the information received
- H04L1/0001—Systems modifying transmission characteristics according to link quality, e.g. power backoff
- H04L1/0009—Systems modifying transmission characteristics according to link quality, e.g. power backoff by adapting the channel coding
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- H—ELECTRICITY
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- H04L1/004—Arrangements for detecting or preventing errors in the information received by using forward error control
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- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
- H04L25/03006—Arrangements for removing intersymbol interference
- H04L25/03343—Arrangements at the transmitter end
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
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- H04L5/00—Arrangements affording multiple use of the transmission path
- H04L5/003—Arrangements for allocating sub-channels of the transmission path
- H04L5/0044—Arrangements for allocating sub-channels of the transmission path allocation of payload
- H04L5/0046—Determination of how many bits are transmitted on different sub-channels
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Abstract
Description
where P′rx(j,k) is the received power for transmission channel (j,k) (i.e., the j-th spatial subchannel of the k-th frequency subchannel), Ptx is the total transmit power available at the transmitter, NT is the number of transmit antennas, NF is the number of frequency subchannels, and H(j,k) is the complex-valued “effective” channel gain from the transmitter system to the receiver system for transmission channel (j,k). For simplicity, the channel gain H(j,k) includes the effects of the processing at the transmitter and receiver. Also for simplicity, it is assumed that the number of spatial subchannels is equal to the number of transmit antennas and NT·NF represents the total number of available transmission channels. If the same amount of power is transmitted for each available transmission channel, the total received power Prx for all available transmission channels may be expressed as:
where c is a factor chosen such that the received powers for all transmission channels are approximately equal at the receiver. As shown in equation (3), the weight for each transmission channel is inversely proportional to that channel's gain. The weighted transmit power for transmission channel (j,k) can then be expressed as:
where b is a “normalization” factor used to distribute the total transmit power among the available transmission channels. This normalization factor b can be expressed as:
where c2=b. As shown in equation (5), the normalization factor b is computed as the sum of the reciprocal power gain for all available transmission channels.
P rx(j,k)=bP tx. Eq (6)
If the noise variance is the same across all transmission channels, then the equal received power allows the modulation symbols for all channels to be generated based on a single common coding and modulation scheme, which then greatly simplify the coding and decoding processes.
The weight for each selected transmission channel is inversely proportional to that channel's gain and is determined such that all selected transmission channels are received at approximately equal power. The weighted transmit power for each transmission channel can then be expressed as:
where α is the threshold and {tilde over (b)} is a normalization factor used to distribute the total transmit power among the selected transmission channels. As shown in equation (9), a transmission channel is selected for use if its power gain is greater than or equal to a power gain threshold (i.e., |H(j,k)|2≧αLave). The normalization factor {tilde over (b)} is computed based on only the selected transmission channels and can be expressed as:
Selective Channel Inversion Based on Channel SNRs
The average received SNR, γave, for each available transmission channel may be expressed as:
which also assumes equal transmit power over the available transmission channels. The received SNR, S, for all available transmission channels may be expressed as:
The received SNR, S, is based on the total transmit power being equally distributed across all available transmission channels.
As shown in equation (15), the normalization factor β is computed based on, and as the sum of the reciprocal of, the SNRs of all selected transmission channels.
where {tilde over (c)}2=β. The weighted transmit power for each transmission channel may then be expressed as:
As shown in equation (17), only transmission channels for which the received SNR is greater than or equal to an SNR threshold (i.e., γ(j,k)≧αγave) is selected for use.
By substituting γave from equation (13) and S from equation (14) into equation (18), the following is obtained:
Each element of the sequence {tilde over (b)}(l) may be used as a normalization factor if the l best transmission channels are selected for use.
where σ2 is the received noise power in a single transmission channel. The largest value of l can be identified by evaluating each value of l starting with 1. For each value of l, the achievable SNR for the l best transmission channels may be determined as shown by the left argument of equation (20). This achievable SNR is then compared against the SNR, zn, required for that code rate rn.
The threshold σ(n) optimizes the throughput for code rate rn, which requires the setpoint zn. Since the same code rate is used for all selected transmission channels, the maximum available throughput, Tn, can be computed as the throughput for each channel (which is rn) times the number of selected channels, ln,max. The maximum available throughput Tn for setpoint zn can be expressed as:
Tn=ln,maxrn, Eq (22)
where the unit for Tn is in information bits per modulation symbol.
T opt=max(T n). Eq (23)
As the code rate increases, more information bits may be transmitted per modulation symbol. However, the required SNR also increases, which requires more transmit power for each selected transmission channel for a given noise variance. Since the total transmit power is limited, fewer transmission channels may be able to achieve the higher required SNR. Thus, the maximum available throughput for each code rate in the vector may be computed, and the code rate that provides the highest throughput may be deemed as the optimum code rate for the specific channel conditions being evaluated. The optimum threshold, αopt, is then equal to the threshold α(n) corresponding to the code rate rn that results in Topt.
β(l)N T N F ≧z n. Eq (25)
Once the largest value of l, ln,max, is determined for code rate rn, the threshold α(n) associated with this code rate may be determined as:
The optimum threshold, αopt, and the optimum throughput, Topt, may also be determined as described above.
TABLE 1 | ||||
Received SNR | # of Information | Modulation | # of Coded | Coding |
Range | Bits/Symbol | Symbol | Bits/Symbol | Rate |
1.5-4.4 | 1 | |
2 | ½ |
4.4-6.4 | 1.5 | |
2 | ¾ |
6.4-8.35 | 2 | 16-QAM | 4 | ½ |
8.35-10.4 | 2.5 | 16-QAM | 4 | ⅝ |
10.4-12.3 | 3 | 16-QAM | 4 | ¾ |
12.3-14.15 | 3.5 | 64-QAM | 6 | 7/12 |
14.15-15.55 | 4 | 64-QAM | 6 | ⅔ |
15.55-17.35 | 4.5 | 64-QAM | 6 | ¾ |
>17.35 | 5 | 64-QAM | 6 | ⅚ |
where b1, b2, . . . and bNc are respectively the weighted modulation symbols for the
eij are elements of an eigenvector matrix E related to the transmission characteristics from the transmit antennas to the receive antennas; and
x1, x2, . . . xN
x 1 =b 1 ·e 11 +b 2 ·e 12 + . . . +b N
x 2 =b 1 ·e 21 +b 2 ·e 22 + . . . +b N
x N
The eigenvector matrix E may be computed by the transmitter or is provided to the transmitter by the receiver. The elements of the matrix E are also taken into account in determining the effective channel gains H(j,k).
Claims (12)
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US12/499,951 US8040965B2 (en) | 2001-05-17 | 2009-07-09 | Method and apparatus for processing data for transmission in a multi-channel communication system using selective channel inversion |
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EP (3) | EP2317664A3 (en) |
JP (3) | JP2004535105A (en) |
KR (2) | KR100942646B1 (en) |
CN (1) | CN1568586B (en) |
AU (1) | AU2002259221A1 (en) |
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EP2317664A2 (en) | 2011-05-04 |
WO2002093779A3 (en) | 2003-02-13 |
KR100942646B1 (en) | 2010-02-17 |
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EP2053773A1 (en) | 2009-04-29 |
WO2002093779A2 (en) | 2002-11-21 |
US8488706B2 (en) | 2013-07-16 |
AU2002259221A1 (en) | 2002-11-25 |
BR0209640A (en) | 2004-08-31 |
KR100919082B1 (en) | 2009-09-28 |
TW576032B (en) | 2004-02-11 |
JP5296042B2 (en) | 2013-09-25 |
JP2009081873A (en) | 2009-04-16 |
US20030048856A1 (en) | 2003-03-13 |
US20100104039A1 (en) | 2010-04-29 |
US20100246704A1 (en) | 2010-09-30 |
JP2004535105A (en) | 2004-11-18 |
JP2011097619A (en) | 2011-05-12 |
US8477858B2 (en) | 2013-07-02 |
CN1568586B (en) | 2010-12-22 |
EP2317664A3 (en) | 2012-10-10 |
EP1389366B1 (en) | 2016-04-20 |
KR20030094420A (en) | 2003-12-11 |
KR20090058595A (en) | 2009-06-09 |
EP1389366A2 (en) | 2004-02-18 |
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