US8275017B2 - Method of packet transmission and reception of quadrature amplitude modulated signals in a frequency hopping radio system - Google Patents
Method of packet transmission and reception of quadrature amplitude modulated signals in a frequency hopping radio system Download PDFInfo
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- US8275017B2 US8275017B2 US12/701,494 US70149410A US8275017B2 US 8275017 B2 US8275017 B2 US 8275017B2 US 70149410 A US70149410 A US 70149410A US 8275017 B2 US8275017 B2 US 8275017B2
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- 238000000034 method Methods 0.000 title claims description 19
- 238000004891 communication Methods 0.000 abstract description 7
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/69—Spread spectrum techniques
- H04B1/713—Spread spectrum techniques using frequency hopping
Definitions
- One embodiment of the present invention is a method of transmitting frequency-hopping quadrature amplitude modulation data signals, comprising: transmitting in each of the quadrature channels at an initial carrier frequency f 0 a first signal over consecutive time intervals T 0S , T PN1 , T 01 and T PN2 comprising: transmitting during the time interval T 0S only a first pilot tone signal
- a 1 Sin ⁇ ( 2 ⁇ ⁇ ⁇ ⁇ f S 2 ⁇ t ) , where an amplitude A 1 is between 0.05 A 0 and 0.1 A 0 , and of a first pseudo noise sequence PN1 multiplied by a cosine signal
- f i f 0 + c i m i ⁇ f S 2 , where c i is a positive or negative integer and m i is a positive integer.
- Another embodiment of the present invention is a method of receiving frequency-hopping quadrature amplitude modulation data signals, comprising: demodulating a received signal and forming two quadrature channels; receiving a pilot signal
- T S is shorter than T 0S and T 1 is longer than T 01 .
- f S 2 is the pilot tone frequency, equal to one half of the symbol clock frequency.
- the time interval T needed to transmit a data packet, is presented as the sum of the following intervals:
- T 0S and T S are the preambles required for carrier and clock frequency synchronization
- T 01 and T 1 are the packet data payloads.
- the overall packet stream is formed by the initial packet at frequency f 0 followed by a number of additional packets at other frequencies defined below.
- the pilot-assisted synchronization method from [3] is used to reduce the initial and subsequent packet synchronization times T 0S and T S , allowing reduction of the overhead and therefore to achieve transmission of more user data symbols in each packet period T.
- a 0 ⁇ sin ⁇ ⁇ 2 ⁇ ⁇ ⁇ ⁇ ⁇ f S 2 ⁇ t is transmitted in both quadrature channels, where f S is the symbol clock frequency and A 0 is the pilot tone amplitude, providing a pilot tone power that is equal to the total signal power during data message transmission. Introduction of this pilot tone reduces the time to acquire synchronization by factors of ten.
- the PN1 sequence samples are orthogonal to the pilot tone
- the sequence PN1 is necessary to define the exact starting time of the actual user data transmission. To eliminate phase ambiguity the PN1 samples are multiplied by the signal
- the interval T PN1 is followed by the interval T 01 or T 1 , within which data symbol samples are transmitted, after multiplication by
- the symbol samples of service data may be transmitted, for example: modulation type, coding rate, combination code of frequency changes and other data.
- the transmission of data symbol samples is carried out within the interval T 1 .
- the interval T 01 or T 1 is followed by the interval T PN2 , during which a PN sequence PN2 is added to the pilot tone
- the final moment of the PN2 sequence defines the moment of a carrier frequency value change. To eliminate phase ambiguity the PN2 sequence samples are multiplied by the signal
- the new carrier frequency value at the end of each of the following data packet transmission intervals T i is determined such that in the i-th interval the carrier frequency is equal to
- c i is a positive or negative integer and m i is a positive integer.
- the exact values of c i and m i are predetermined and known to both transmitter and receiver. Knowledge of this predetermined law governing carrier frequency changes on the receiving end enables, knowing the exact values of f 0 and f S , prediction in the receiving equipment of the exact carrier frequency value corresponding to the i-th receiving interval. This results in a significant reduction (by factors of 10 or more) of the synchronization acquisition interval T S when the packet transmission is made at carrier frequencies other than f 0 . By this method, the increase of packet transmission channel bandwidth is achieved.
- the input signal is then multiplied by the signal
- T T S +T PN1 +T 1 +T PN2 ; at this T S ⁇ T 0S , which allows a substantial increase in the carrier frequency bandwidth capacity.
- T PN 1 50 clock frequency samples
- T 01 4 ⁇ 10 3 clock frequency samples
- T PN 2 50 clock frequency samples
- the packet length T is equal to 6100 samples and at the initial frequency f 0 the number of data samples is 4000.
- T 1 At other carrier frequencies with T S equal, for example, to 100 clock frequency samples, and with the total packet length T unchanged, T 1 will be equal to 5900 data samples. These packets contain 47.5% more data than the initial packet and the gain is therefore a factor of 1.475 times.
Abstract
Description
where fS is a symbol clock frequency and A0 is an amplitude, at a power equal to a total signal power during data transmission; transmitting during the time interval TPN1 a sum of a second pilot tone signal
where an amplitude A1 is between 0.05 A0 and 0.1 A0, and of a first pseudo noise sequence PN1 multiplied by a cosine signal
transmitting during the time interval T01 a sum of the second pilot tone signal and of a first symbol data sequence multiplied by the cosine signal; transmitting during the time interval TPN2, a sum of the second pilot tone signal and of a second pseudo noise sequence PN2 multiplied by the cosine signal; after transmitting the first signal, transmitting in each of the quadrature channels at an second carrier frequency fi a second signal over consecutive time intervals TS, TPN1, T1 and TPN2 comprising: transmitting during the time interval TS only the first pilot tone signal at the power equal to the total signal power during data transmission; transmitting during the time interval TPN1 a sum of the second pilot tone signal, and of the first pseudo noise sequence PN1 multiplied by the cosine signal; transmitting during the time interval T1 a sum of the second pilot tone signal and of a second symbol data sequence multiplied by the cosine signal; and transmitting during the time interval TPN2, a sum of the second pilot tone signal and of the second pseudo noise sequence PN2 multiplied by the cosine signal; wherein TS is shorter than T0S and T1 is longer than T01; and wherein the second carrier frequency
where ci is a positive or negative integer and mi is a positive integer.
where fS is a symbol clock frequency, during a time interval T0S, for synchronization of a carrier frequency and a clock frequency; in each of the quadrature channels, during a time interval TPN1, after the T0S, multiplying the received signal by a cosine signal
and applying a filter corresponding to a first pseudo noise sequence PN1 to determine a starting time of a first transmitted data symbol sequence; in each of the quadrature channels, during a time interval T01, after the TPN1, multiplying the received signal by the cosine signal to recover the first transmitted data symbol sequence; in each of the quadrature channels, during a time interval TPN2, after the T01, multiplying the received signal by the cosine signal and applying a filter corresponding to a second pseudo noise sequence PN2 to determine a moment of a first carrier frequency switch; switching carrier frequency at the moment of the first carrier frequency switch; after the first carrier frequency switch, receiving the pilot signal, during a time interval TS, for synchronization of the carrier frequency and the clock frequency; in each of the quadrature channels, during a time interval TPN1, after the TS, multiplying the received signal by the cosine signal and applying the filter corresponding to the PN1 to determine a starting time of a second transmitted data symbol sequence; in each of the quadrature channels, during a time interval T1, after the TPN1, multiplying the received signal by the cosine signal to recover the second transmitted data symbol sequence; and in each of the quadrature channels, during a time interval TPN2, after the T1, multiplying the received signal by the cosine signal and applying the filter corresponding to the PN2 to determine a moment of a second carrier frequency switch; wherein during all the time intervals except T0S synchronizing the carrier frequency and a symbol frequency is using a pilot signal
and wherein TS is shorter than T0S and T1 is longer than T01.
where A1 is the pilot tone amplitude, which defines its power and which amounts to only a small percentage of the main signal power;
is the pilot tone frequency, equal to one half of the symbol clock frequency.
is transmitted in both quadrature channels, where fS is the symbol clock frequency and A0 is the pilot tone amplitude, providing a pilot tone power that is equal to the total signal power during data message transmission. Introduction of this pilot tone reduces the time to acquire synchronization by factors of ten.
The sequence PN1 is necessary to define the exact starting time of the actual user data transmission. To eliminate phase ambiguity the PN1 samples are multiplied by the signal
before being added to the pilot tone.
and added to
The symbol samples are orthogonal to the pilot tone
Within the interval T01 the symbol samples of service data may be transmitted, for example: modulation type, coding rate, combination code of frequency changes and other data. The transmission of data symbol samples is carried out within the interval T1.
The final moment of the PN2 sequence defines the moment of a carrier frequency value change. To eliminate phase ambiguity the PN2 sequence samples are multiplied by the signal
before being added to the pilot tone.
has been received during the interval T0S, receiver side synchronization of carrier and clock frequencies occurs. After this, within the interval TPN1 the multiplication of input signal by the signal
takes place, and using a filter matched to the PN1 sequence, the exact moment the data symbol sequence commences in the received signal is determined. The PN1 sequence base is equal to 50 or greater, and the reception of the PN1 sequence is realized in the both quadrature channels. The use of a filter matched to the PN1 sequence to process the received signal within the interval TPN1 makes it possible to obtain a sample with a signal to noise ratio higher than at the input of the matched filter, by 20 dB at the end of the interval TPN1. This allows precise determination of the start of the data sequence.
within the interval T01, following the interval TPN1, resulting in the service data symbol sequence.
and with the help of a filter matched to the PN2 sequence, during the time TPN2 the exact moment of switching carrier frequency is determined. Its new value is determined according to the predetermined known parameters ci and mi.
it will be equal to T=TS+TPN1+T1+TPN2; at this TS<<T0S, which allows a substantial increase in the carrier frequency bandwidth capacity.
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US12/701,494 US8275017B2 (en) | 2009-02-05 | 2010-02-05 | Method of packet transmission and reception of quadrature amplitude modulated signals in a frequency hopping radio system |
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US15010509P | 2009-02-05 | 2009-02-05 | |
US12/701,494 US8275017B2 (en) | 2009-02-05 | 2010-02-05 | Method of packet transmission and reception of quadrature amplitude modulated signals in a frequency hopping radio system |
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US9448670B2 (en) * | 2012-12-31 | 2016-09-20 | Broadcom Corporation | Methods and systems for hybrid multi-touch capacitive (MTC) and active stylus touch device |
CN104159306B (en) * | 2014-07-22 | 2018-05-29 | 华为技术有限公司 | A kind of method, equipment and system for controlling interface-free resources |
EP3591851A1 (en) * | 2018-07-02 | 2020-01-08 | Semtech Corporation | Relative frequency hops in low-power, wide-area network |
CN110518957B (en) * | 2019-07-30 | 2020-11-06 | 北京大学 | Bypass network guiding method in open wireless channel |
Citations (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US5537434A (en) | 1993-10-25 | 1996-07-16 | Telefonaktiebolaget Lm Ericsson | Frequency hopping control channel in a radio communication system |
US5586141A (en) | 1993-06-02 | 1996-12-17 | Vtech Communications, Ltd. | Interface protocol method for use in a frequency hopping radio system having first hopping code for synchronization and second hopping code for communication |
WO2005096539A1 (en) | 2004-03-30 | 2005-10-13 | Modesat Communications Ou | System and method for transmission and reception of qam signals at low signal to noise ratio |
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Patent Citations (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US5586141A (en) | 1993-06-02 | 1996-12-17 | Vtech Communications, Ltd. | Interface protocol method for use in a frequency hopping radio system having first hopping code for synchronization and second hopping code for communication |
US5537434A (en) | 1993-10-25 | 1996-07-16 | Telefonaktiebolaget Lm Ericsson | Frequency hopping control channel in a radio communication system |
WO2005096539A1 (en) | 2004-03-30 | 2005-10-13 | Modesat Communications Ou | System and method for transmission and reception of qam signals at low signal to noise ratio |
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