USRE40016E1 - Power factor correction control circuit - Google Patents

Power factor correction control circuit Download PDF

Info

Publication number
USRE40016E1
USRE40016E1 US10/870,901 US87090104A USRE40016E US RE40016 E1 USRE40016 E1 US RE40016E1 US 87090104 A US87090104 A US 87090104A US RE40016 E USRE40016 E US RE40016E
Authority
US
United States
Prior art keywords
inductor
time
switch
power factor
factor control
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Lifetime
Application number
US10/870,901
Inventor
Thomas J. Ribarich
Robert Marenche
Dana S. Wilhelm
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Infineon Technologies North America Corp
Original Assignee
International Rectifier Corp USA
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by International Rectifier Corp USA filed Critical International Rectifier Corp USA
Priority to US10/870,901 priority Critical patent/USRE40016E1/en
Application granted granted Critical
Publication of USRE40016E1 publication Critical patent/USRE40016E1/en
Assigned to Infineon Technologies Americas Corp. reassignment Infineon Technologies Americas Corp. CHANGE OF NAME (SEE DOCUMENT FOR DETAILS). Assignors: INTERNATIONAL RECTIFIER CORPORATION
Anticipated expiration legal-status Critical
Expired - Lifetime legal-status Critical Current

Links

Images

Classifications

    • HELECTRICITY
    • H02GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02MAPPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00Details of apparatus for conversion
    • H02M1/42Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208Arrangements for improving power factor of AC input
    • H02M1/4225Arrangements for improving power factor of AC input using a non-isolated boost converter
    • YGENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02BCLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
    • YGENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02PCLIMATE CHANGE MITIGATION TECHNOLOGIES IN THE PRODUCTION OR PROCESSING OF GOODS
    • Y02P80/00Climate change mitigation technologies for sector-wide applications
    • Y02P80/10Efficient use of energy, e.g. using compressed air or pressurized fluid as energy carrier

Definitions

  • the present invention relates to power factor correction for AC to DC power converters, and more specifically, to AC to DC power converters having power factor correction circuitry utilizing a minimal component count and minimal IC pin count without loss of performance.
  • PFC active power factor correction
  • THD and power factor (PF) represent performance measurements of how well the PFC circuit works.
  • a power factor (PF) of 1.0 represents the highest achievable, and a THD lower than about 15% is acceptable in practice.
  • Circuit 2 has a boost-type converter topology and a PFC IC 4 such as the Motorola 34262.
  • the resulting circuit requires a voltage divider network (resistors 6 and 8 and capacitor 10 ) for sensing the AC rectified line input.
  • a secondary winding on the boost inductor 12 detects the zero-crossing of the inductor current.
  • a current sensing resistor 14 in the source of the boost switch 16 shapes the peak inductor current and detects an over-current condition.
  • a voltage-divider network (resistors 18 and 20 ) senses and regulates a constant DC bus voltage and detects an over-voltage condition due to load transients.
  • a compensation capacitor 22 is required for a stable loop response.
  • the present invention overcomes the deficiencies of the prior art by providing a new control method that results in a minimal component count, minimal IC pin count, and the same performance as standard PFC ICs available on the market.
  • the power factor control circuit of the present invention includes an inductor for receiving AC rectified power and a switch for charging/discharging the inductor.
  • a switching circuit connected to the inductor controls the on-time of the switch, and thereby the charging time of the inductor, by comparing a DC bus voltage to a fixed reference voltage.
  • the switching circuit also controls the off-time of the switch, and thereby the discharging time of the inductor, by turning the switch off until the inductor current discharges to zero, as detected by the switching circuit, such that the off-time of the switch varies as a function of the peak inductor current during each switching cycle.
  • the switch is a MOSFET
  • the inductor includes a secondary winding which is used by the switching circuit to determine the inductor current.
  • the MOSFET operates without a current-sensing resistor connected in series with the source of the MOSFET.
  • the on-time of the switch is modulated as a function of the off-time of the switch to achieve lower total harmonic distortion.
  • the current in the inductor follows the sinusoidal voltage of the AC rectified power as the switching circuit is turned on and off at a much higher frequency than the line frequency of the AC rectified power, thereby eliminating the need to sense the rectified AC line input voltage.
  • FIG. 1 is a circuit diagram showing a prior art power factor control circuit of an AC to DC power converter.
  • FIG. 2 is a circuit diagram showing a power factor control circuit according to the present invention.
  • FIG. 3 is a circuit diagram showing an AC to DC power converter incorporating a power factor control circuit according to the present invention.
  • FIG. 4 is a timing diagram for the circuit of FIG. 3 .
  • Circuit 30 includes IC 32 .
  • a secondary winding on the boost inductor 34 detects the zero-crossing of the inductor current.
  • no current sensing resistor is required in series with the source of MOSFET 36 .
  • a voltage-divider network (resistors 38 and 40 ) senses and regulates a constant DC bus voltage and detects an over-voltage condition due to load transients.
  • a compensation capacitor 22 provides a stable loop response.
  • FIG. 3 shows the circuitry within IC 32 , wherein like elements are identified by like reference numerals.
  • FIG. 4 The corresponding timing diagram for the invention is shown in FIG. 4 .
  • the circuit of the present invention is classified as running in critical continuous mode, in which the inductor current discharges to zero during each switching cycle.
  • the functionality of the circuit relies on the fact that there is no need to sense the rectified AC line input voltage because it is already sinusoidal. Therefore, the current in inductor 34 will naturally follow the sinusoidal voltage envelope as the boost MOSFET 36 is turned on and off at a much higher frequency (>10 kHZ) than the input line frequency ( ⁇ 50-60 Hz).
  • the circuit of the present invention compares the DC bus voltage to a fixed reference voltage (Vref) to determine the charging time of the boost inductor 34 (or on-time of the boost switch 36 ). The circuit then turns off the boost switch 36 until the inductor current discharges to zero, as detected by the secondary winding 35 on the boost inductor 34 .
  • Vref fixed reference voltage
  • the on-time is controlled by the DC bus and the off-time changes as a function of how high the peak inductor charges each switching cycle.
  • the result is a system where the switching frequency is free-running and constantly changing from a higher frequency near the zero-crossings of AC input line voltage, to a lower frequency at the peaks.
  • a further improvement to the circuit, to achieve a low total harmonic distortion (THD), involves dynamically modulating the on-time as a function of the off-time. All of these functions are described in more detail in the following text.
  • the inductor current charges up until the sawtooth voltage (VSAW), resulting from capacitor 62 being charged by the current mirror comprised of transistors 64 and 66 , reaches the output voltage (VDC′) from the DC bus feedback circuitry. Once this occurs, the set input S of latch 58 goes high causing the Q output to go “high” and the boost MOSFET 54 to turn off. The Q output of latch 58 also discharges capacitor 62 through OR gate 68 and MOSFET 70 , and the Q output of latch 58 forces the reset input R of latch 72 “low”, therefore freeing latch 72 .
  • VSAW sawtooth voltage
  • VDC′ output voltage
  • the boost MOSFET 36 When the boost MOSFET 36 turns off, the secondary winding output 35 of the boost inductor 34 goes “high,” causing the output of comparator 74 to go “high,” as well as the S input of latch 72 . During this “off” time, the inductor current discharges into the DC bus capacitor 76 through diode 78 and the modulation capacitor 80 charges up through current source 82 .
  • the voltage on capacitor 80 then remains constant for the duration of the on time. This voltage is converted to a current through OPAMP 88 , transistor 90 , and variable resistor 92 , and defines the charging current for capacitor 62 . As the off-time varies for each switching cycle, so does the voltage on capacitor 80 , and therefore the rate at which capacitor 62 charges. By adjusting the modulation gain with resistor 92 , the amount of modulation of the on-time as a function of the off-time can be controlled. The longer the off-time, the higher capacitor 80 charges, the higher the current charging capacitor 62 , the faster capacitor 62 reaches the VDC threshold, and the shorter the on-time of boost MOSFET 54 .
  • the voltage on capacitor 80 is discharged to zero at the beginning of each offtime with a pulse generator (PGEN 1 ) 94 and MOSFET 96 .
  • OPAMP 98 and biasing resistors 100 and 102 and capacitor 104 determine the gain and speed of the feedback loop for the DC bus regulation.

Abstract

A power factor control circuit for an AC to DC power converter includes an inductor receiving AC rectified power. The charging time of the inductor is controlled by a switching circuit based on a comparison between a DC bus voltage and a fixed reference voltage. The circuit operates without an AC rectified line sensing network, and without a current-sensing resistor connected to the source of the MOSFET switch.

Description

This application claims the benefit of U.S. Provisional Application Serial No. 60/142,949 filed Jul. 12, 1999.
BACKGROUND OF THE INVENTION
1. Field of the Invention
The present invention relates to power factor correction for AC to DC power converters, and more specifically, to AC to DC power converters having power factor correction circuitry utilizing a minimal component count and minimal IC pin count without loss of performance.
2. Brief Description of the Related Art
In most AC to DC power converters, it is convenient to have the circuit act as a pure resistor to the AC input line voltage. To achieve this, active power factor correction (PFC) can be implemented which, for an AC input line voltage, produces an AC input line current.
It also is important to produce a sinusoidal input current which has a low total harmonic distortion (THD). THD and power factor (PF) represent performance measurements of how well the PFC circuit works. A power factor (PF) of 1.0 represents the highest achievable, and a THD lower than about 15% is acceptable in practice.
A typical solution for providing active power factor correction is shown in circuit 2 of FIG. 1. Circuit 2 has a boost-type converter topology and a PFC IC 4 such as the Motorola 34262. The resulting circuit requires a voltage divider network (resistors 6 and 8 and capacitor 10) for sensing the AC rectified line input. Additionally, a secondary winding on the boost inductor 12 detects the zero-crossing of the inductor current. Also, a current sensing resistor 14 in the source of the boost switch 16 shapes the peak inductor current and detects an over-current condition. A voltage-divider network (resistors 18 and 20) senses and regulates a constant DC bus voltage and detects an over-voltage condition due to load transients. A compensation capacitor 22 is required for a stable loop response.
Accordingly, the need exists in the prior art for implementation of a simpler active power factor correction (PFC) circuit having fewer components.
SUMMARY OF THE INVENTION
The present invention overcomes the deficiencies of the prior art by providing a new control method that results in a minimal component count, minimal IC pin count, and the same performance as standard PFC ICs available on the market.
The power factor control circuit of the present invention includes an inductor for receiving AC rectified power and a switch for charging/discharging the inductor. A switching circuit connected to the inductor controls the on-time of the switch, and thereby the charging time of the inductor, by comparing a DC bus voltage to a fixed reference voltage. The switching circuit also controls the off-time of the switch, and thereby the discharging time of the inductor, by turning the switch off until the inductor current discharges to zero, as detected by the switching circuit, such that the off-time of the switch varies as a function of the peak inductor current during each switching cycle. Preferably the switch is a MOSFET, and the inductor includes a secondary winding which is used by the switching circuit to determine the inductor current.
Advantageously, the MOSFET operates without a current-sensing resistor connected in series with the source of the MOSFET. Further, the on-time of the switch is modulated as a function of the off-time of the switch to achieve lower total harmonic distortion. In addition, the current in the inductor follows the sinusoidal voltage of the AC rectified power as the switching circuit is turned on and off at a much higher frequency than the line frequency of the AC rectified power, thereby eliminating the need to sense the rectified AC line input voltage.
BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1 is a circuit diagram showing a prior art power factor control circuit of an AC to DC power converter.
FIG. 2 is a circuit diagram showing a power factor control circuit according to the present invention.
FIG. 3 is a circuit diagram showing an AC to DC power converter incorporating a power factor control circuit according to the present invention.
FIG. 4 is a timing diagram for the circuit of FIG. 3.
DETAILED DESCRIPTION OF PREFERRED EMBODIMENTS
Referring to FIG. 2, the power factor correction circuit 30 of the present invention is shown. Circuit 30 includes IC 32. A secondary winding on the boost inductor 34 detects the zero-crossing of the inductor current. Unlike the prior art circuit shown in FIG. 1, in the circuit of the present invention, no current sensing resistor is required in series with the source of MOSFET 36. A voltage-divider network (resistors 38 and 40) senses and regulates a constant DC bus voltage and detects an over-voltage condition due to load transients. A compensation capacitor 22 provides a stable loop response.
The invention will be described in further detail with reference to FIG. 3, which shows the circuitry within IC 32, wherein like elements are identified by like reference numerals. The corresponding timing diagram for the invention is shown in FIG. 4. The circuit of the present invention is classified as running in critical continuous mode, in which the inductor current discharges to zero during each switching cycle. The functionality of the circuit relies on the fact that there is no need to sense the rectified AC line input voltage because it is already sinusoidal. Therefore, the current in inductor 34 will naturally follow the sinusoidal voltage envelope as the boost MOSFET 36 is turned on and off at a much higher frequency (>10 kHZ) than the input line frequency (˜50-60 Hz).
The circuit of the present invention compares the DC bus voltage to a fixed reference voltage (Vref) to determine the charging time of the boost inductor 34 (or on-time of the boost switch 36). The circuit then turns off the boost switch 36 until the inductor current discharges to zero, as detected by the secondary winding 35 on the boost inductor 34.
The on-time is controlled by the DC bus and the off-time changes as a function of how high the peak inductor charges each switching cycle. The result is a system where the switching frequency is free-running and constantly changing from a higher frequency near the zero-crossings of AC input line voltage, to a lower frequency at the peaks.
A further improvement to the circuit, to achieve a low total harmonic distortion (THD), involves dynamically modulating the on-time as a function of the off-time. All of these functions are described in more detail in the following text.
When the circuit is first enabled (ENABLE signal goes logic “high”) the Q output of latch 58 is low, both inputs of the AND gate 60 are high, and the boost MOSFET 36 is turned on. The boost inductor 37 is shorted to ground and begins charging (see Timing Diagram, FIG. 4).
The inductor current charges up until the sawtooth voltage (VSAW), resulting from capacitor 62 being charged by the current mirror comprised of transistors 64 and 66, reaches the output voltage (VDC′) from the DC bus feedback circuitry. Once this occurs, the set input S of latch 58 goes high causing the Q output to go “high” and the boost MOSFET 54 to turn off. The Q output of latch 58 also discharges capacitor 62 through OR gate 68 and MOSFET 70, and the Q output of latch 58 forces the reset input R of latch 72 “low”, therefore freeing latch 72.
When the boost MOSFET 36 turns off, the secondary winding output 35 of the boost inductor 34 goes “high,” causing the output of comparator 74 to go “high,” as well as the S input of latch 72. During this “off” time, the inductor current discharges into the DC bus capacitor 76 through diode 78 and the modulation capacitor 80 charges up through current source 82.
When the boost inductor current discharges to zero, secondary winding output 56 goes “low”, causing the output of NOR gate 84 to go “high,” and therefore the reset input R of latch 58 goes “high” and the boost MOSFET 36 turns on again, and the boost inductor 37 charges again. The transition of secondary winding output 35 to “low” also turns MOSFET 86 off, therefore turning the current source 82 off as well.
The voltage on capacitor 80 then remains constant for the duration of the on time. This voltage is converted to a current through OPAMP 88, transistor 90, and variable resistor 92, and defines the charging current for capacitor 62. As the off-time varies for each switching cycle, so does the voltage on capacitor 80, and therefore the rate at which capacitor 62 charges. By adjusting the modulation gain with resistor 92, the amount of modulation of the on-time as a function of the off-time can be controlled. The longer the off-time, the higher capacitor 80 charges, the higher the current charging capacitor 62, the faster capacitor 62 reaches the VDC threshold, and the shorter the on-time of boost MOSFET 54.
Inversely, the shorter the off-time, the longer the on-time. This modulation effect changes dynamically over each cycle of the low-frequency AC line input voltage, with the on-time being slightly longer at the zero-crossings than at the peaks. Compared to a fixed on-time over the entire cycle, the modulated solution results in a “flatter” envelope with less cross-over distortion in the line current which gives lower total harmonic distortion (THD).
The voltage on capacitor 80 is discharged to zero at the beginning of each offtime with a pulse generator (PGEN1) 94 and MOSFET 96. OPAMP 98 and biasing resistors 100 and 102 and capacitor 104 determine the gain and speed of the feedback loop for the DC bus regulation.
Although the present invention has been descried in relation to particular embodiments thereof, many other variations and modifications and other uses will become apparent to those skilled in the art. Therefore, the present invention is to be limited not by the specific disclosure herein, but only by the appended claims.

Claims (12)

1. A power factor control circuit for an AC to DC power converter, the circuit comprising:
an inductor configured to receive AC rectified power from an AC line input voltage; and
a switching circuit connected to the inductor and including a switch for switching current through the inductor on and off;
the switching circuit controlling the on-time of the switch, and thereby the charging time of the inductor, by comparing a DC bus voltage to a fixed reference voltage,
the switching circuit controlling the off-time of the switch, and thereby the discharging time of the inductor, by turning the switch off until the inductor current discharges to zero, as detected by the switching circuit, such that the off-time of the switch varies as a function of the peak inductor current during each switching cycle,
wherein the on-time of the switch is controlled to be longer at the zero crossings of the AC line input voltage thereby to achieve lower total harmonic distortion.
2. The power factor control circuit of claim 1, wherein the switch comprises a MOSFET.
3. The power factor control circuit of claim 2, wherein the MOSFET operates without a current-sensing resistor connected in series with the source of the MOSFET.
4. The power factor control circuit of claim 1, wherein the on-time of the switch is modulated as a function of the off-time of the switch to achieve lower total harmonic distortion.
5. The power factor control circuit of claim 1, wherein the current in the inductor follows the sinusoidal voltage of the AC rectified power as the switching circuit is turned on and off at a much higher frequency than the line frequency of the AC rectified power, thereby eliminating the need to sense the rectified AC line input voltage.
6. The power factor control circuit of claim 1, wherein the inductor includes a secondary winding which is used by the switching circuit to determine the inductor current.
7. A method of power factor control in an AC to DC power converter using a power factor control circuit having an inductor configured to receive AC rectified power from an AC line input voltage; and a switching circuit connected to the inductor and having a switch for switching current through the inductor on and off, the method comprising the steps of:
controlling the on-time of the switch, and thereby the charging time of the inductor, by comparing a DC bus voltage to a fixed reference voltage,
controlling the off-time of the switch, and thereby the discharging time of the inductor, by turning the switch off until the inductor current discharges to zero, as detected by the switching circuit, such that the off-time of the switch varies as a function of the peak inductor current during each switching cycle, further comprising increasing the on-time of the switch at the zero crossings of the AC line input voltage thereby to achieve lower total harmonic distortion.
8. The method of power factor control of claim 7, wherein the switch comprises a MOSFET.
9. The method of power factor control of claim 8, wherein the on-time and off-time of the MOSFET are controlled without a current-sensing resistor connected in series with the source of the MOSFET.
10. The method of power factor control of claim 7, wherein the on-time of the switching circuit is modulated as a function of the off-time to achieve lower total harmonic distortion.
11. The method of power factor control of claim 7, wherein the current in the inductor follows the sinusoidal voltage of the AC rectified power as the switching circuit is turned on and off at a much higher frequency than the line frequency of the AC rectified power, thereby eliminating the need to sense the rectified AC line input voltage.
12. The method of power factor control of claim 7, wherein the inductor includes a secondary winding which is used by the switching circuit to determine the inductor current.
US10/870,901 1999-07-12 2004-06-18 Power factor correction control circuit Expired - Lifetime USRE40016E1 (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
US10/870,901 USRE40016E1 (en) 1999-07-12 2004-06-18 Power factor correction control circuit

Applications Claiming Priority (3)

Application Number Priority Date Filing Date Title
US14294999P 1999-07-12 1999-07-12
US09/613,252 US6259614B1 (en) 1999-07-12 2000-07-10 Power factor correction control circuit
US10/870,901 USRE40016E1 (en) 1999-07-12 2004-06-18 Power factor correction control circuit

Related Parent Applications (1)

Application Number Title Priority Date Filing Date
US09/613,252 Reissue US6259614B1 (en) 1999-07-12 2000-07-10 Power factor correction control circuit

Publications (1)

Publication Number Publication Date
USRE40016E1 true USRE40016E1 (en) 2008-01-22

Family

ID=22501926

Family Applications (2)

Application Number Title Priority Date Filing Date
US09/613,252 Ceased US6259614B1 (en) 1999-07-12 2000-07-10 Power factor correction control circuit
US10/870,901 Expired - Lifetime USRE40016E1 (en) 1999-07-12 2004-06-18 Power factor correction control circuit

Family Applications Before (1)

Application Number Title Priority Date Filing Date
US09/613,252 Ceased US6259614B1 (en) 1999-07-12 2000-07-10 Power factor correction control circuit

Country Status (3)

Country Link
US (2) US6259614B1 (en)
JP (1) JP3406897B2 (en)
DE (1) DE10032846A1 (en)

Cited By (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20100046262A1 (en) * 2008-08-21 2010-02-25 Leadtrend Technology Corporation Control Apparatus and Control Method for a Power Factor Correction Power Converter
US20100118573A1 (en) * 2008-11-07 2010-05-13 Power Integrations, Inc. Method and apparatus to increase efficiency in a power factor correction circuit
US20100118571A1 (en) * 2008-11-07 2010-05-13 Power Integrations, Inc. Method and apparatus to control a power factor correction circuit
US7923973B2 (en) 2008-09-15 2011-04-12 Power Integrations, Inc. Method and apparatus to reduce line current harmonics from a power supply
US8467209B2 (en) 2010-07-27 2013-06-18 Stmicroelectronics S.R.L. Control device of a switching power supply
US20140132191A1 (en) * 2012-11-15 2014-05-15 Samsung Electro-Mechanics Co., Ltd. Power factor correction apparatus, power supplying apparatus and motor driving apparatus having the same
US9154030B2 (en) 2012-01-26 2015-10-06 Stmicroelectronics S.R.L. Control device of a switching power supply
US9461558B2 (en) 2012-01-26 2016-10-04 Stmicroelectronics S.R.L. Control device of a switching power supply
US9705412B2 (en) 2015-02-26 2017-07-11 Stmicroelectronics S.R.L. Pulsed feedback switching converter
US10439508B2 (en) 2010-07-27 2019-10-08 Stmicroelectronics S.R.L. Control device of a switching power supply

Families Citing this family (97)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2003017453A1 (en) * 2001-08-16 2003-02-27 Green Power Technologies Ltd. Pfc apparatus for a converter operating in the borderline conduction mode
US6469917B1 (en) 2001-08-16 2002-10-22 Green Power Technologies Ltd. PFC apparatus for a converter operating in the borderline conduction mode
ES2274910T3 (en) * 2001-12-12 2007-06-01 Semiconductor Components Industries, Llc CIRCUIT AND FREQUENCY CONTROLLED FACTOR CORRECTION PROCEDURE.
US6728121B2 (en) * 2002-05-31 2004-04-27 Green Power Technologies Ltd. Method and apparatus for active power factor correction with minimum input current distortion
US6956336B2 (en) * 2002-07-22 2005-10-18 International Rectifier Corporation Single chip ballast control with power factor correction
US7061195B2 (en) * 2002-07-25 2006-06-13 International Rectifier Corporation Global closed loop control system with dv/dt control and EMI/switching loss reduction
DE10241836A1 (en) * 2002-09-09 2004-03-25 Hilti Ag Power factor correction circuit for d.c. current load has electronic power switch between choke, diode, reference potential controlled by circuit with arrangement for detecting null value of current
US6781352B2 (en) 2002-12-16 2004-08-24 International Rectifer Corporation One cycle control continuous conduction mode PFC boost converter integrated circuit with integrated power switch and boost converter
US7015682B2 (en) * 2003-01-30 2006-03-21 Hewlett-Packard Development Company, L.P. Control of a power factor corrected switching power supply
US7126288B2 (en) * 2003-05-05 2006-10-24 International Rectifier Corporation Digital electronic ballast control apparatus and method
TWI238303B (en) * 2003-05-09 2005-08-21 Richtek Techohnology Corp Switching voltage regulator and method for improving load transient efficiency
US7305191B2 (en) * 2003-09-22 2007-12-04 Motorola, Inc. Optical correlator system and supporting method and apparatus
US7038435B2 (en) * 2003-11-24 2006-05-02 Raytheon Company Method for input current regulation and active-power filter with input voltage feedforward and output load feedforward
EP1580638B1 (en) * 2004-03-22 2008-05-14 STMicroelectronics S.r.l. Transition mode power factor correction device in switching power supplies
EP1580639B1 (en) * 2004-03-22 2008-05-14 STMicroelectronics S.r.l. Transition mode power factor correction device in switching power supplies
GB0413494D0 (en) * 2004-06-16 2004-07-21 Elantec Semiconductor Inc Non-Leb restricted DC-DC converter
US7019503B1 (en) * 2005-02-07 2006-03-28 Raytheon Company Active power filter with input voltage feedforward, output load feedforward, and output voltage feedforward
US7432661B2 (en) * 2005-05-02 2008-10-07 Lutron Electronics Co., Inc. Electronic ballast having a flyback cat-ear power supply
CN100362735C (en) * 2005-08-24 2008-01-16 海信集团有限公司 Power supply circuit with PFC inductance and TV set comprising said power supply circuit
US8174855B2 (en) * 2005-10-12 2012-05-08 International Rectifier Corporation Power factor correction integrated circuit with critical conduction mode
JP2007109661A (en) * 2005-10-12 2007-04-26 Internatl Rectifier Corp Integrated circuit for improving power factor with eight pins and controlling ballast
US7750580B2 (en) * 2006-10-06 2010-07-06 U Lighting Group Co Ltd China Dimmable, high power factor ballast for gas discharge lamps
US8362838B2 (en) * 2007-01-19 2013-01-29 Cirrus Logic, Inc. Multi-stage amplifier with multiple sets of fixed and variable voltage rails
DE102007035606B4 (en) 2007-02-08 2017-09-14 Infineon Technologies Austria Ag Method for driving and drive circuit for a switch of a power factor correction circuit
US8076920B1 (en) 2007-03-12 2011-12-13 Cirrus Logic, Inc. Switching power converter and control system
US7667408B2 (en) 2007-03-12 2010-02-23 Cirrus Logic, Inc. Lighting system with lighting dimmer output mapping
US7852017B1 (en) 2007-03-12 2010-12-14 Cirrus Logic, Inc. Ballast for light emitting diode light sources
US8018171B1 (en) 2007-03-12 2011-09-13 Cirrus Logic, Inc. Multi-function duty cycle modifier
US7683595B2 (en) 2007-04-10 2010-03-23 Infineon Technologies Austria Ag Method for actuation, and actuating circuit for a switch in a power factor correction circuit
US7696913B2 (en) 2007-05-02 2010-04-13 Cirrus Logic, Inc. Signal processing system using delta-sigma modulation having an internal stabilizer path with direct output-to-integrator connection
US7554473B2 (en) 2007-05-02 2009-06-30 Cirrus Logic, Inc. Control system using a nonlinear delta-sigma modulator with nonlinear process modeling
US8102127B2 (en) 2007-06-24 2012-01-24 Cirrus Logic, Inc. Hybrid gas discharge lamp-LED lighting system
US8950206B2 (en) 2007-10-05 2015-02-10 Emerson Climate Technologies, Inc. Compressor assembly having electronics cooling system and method
US7895003B2 (en) 2007-10-05 2011-02-22 Emerson Climate Technologies, Inc. Vibration protection in a variable speed compressor
US20090241592A1 (en) * 2007-10-05 2009-10-01 Emerson Climate Technologies, Inc. Compressor assembly having electronics cooling system and method
US8448459B2 (en) 2007-10-08 2013-05-28 Emerson Climate Technologies, Inc. System and method for evaluating parameters for a refrigeration system with a variable speed compressor
US8459053B2 (en) 2007-10-08 2013-06-11 Emerson Climate Technologies, Inc. Variable speed compressor protection system and method
US9541907B2 (en) 2007-10-08 2017-01-10 Emerson Climate Technologies, Inc. System and method for calibrating parameters for a refrigeration system with a variable speed compressor
US8418483B2 (en) 2007-10-08 2013-04-16 Emerson Climate Technologies, Inc. System and method for calculating parameters for a refrigeration system with a variable speed compressor
US8539786B2 (en) 2007-10-08 2013-09-24 Emerson Climate Technologies, Inc. System and method for monitoring overheat of a compressor
KR100949880B1 (en) * 2007-10-31 2010-03-26 주식회사 하이닉스반도체 Semicoductor device and Method of fabricating the same
JP2011504720A (en) 2007-11-26 2011-02-10 コーニンクレッカ フィリップス エレクトロニクス エヌ ヴィ Power factor control circuit and main power supply
US7804697B2 (en) * 2007-12-11 2010-09-28 Cirrus Logic, Inc. History-independent noise-immune modulated transformer-coupled gate control signaling method and apparatus
US7755525B2 (en) * 2008-01-30 2010-07-13 Cirrus Logic, Inc. Delta sigma modulator with unavailable output values
US8022683B2 (en) * 2008-01-30 2011-09-20 Cirrus Logic, Inc. Powering a power supply integrated circuit with sense current
US8008898B2 (en) 2008-01-30 2011-08-30 Cirrus Logic, Inc. Switching regulator with boosted auxiliary winding supply
US8576589B2 (en) * 2008-01-30 2013-11-05 Cirrus Logic, Inc. Switch state controller with a sense current generated operating voltage
US7759881B1 (en) 2008-03-31 2010-07-20 Cirrus Logic, Inc. LED lighting system with a multiple mode current control dimming strategy
US8008902B2 (en) * 2008-06-25 2011-08-30 Cirrus Logic, Inc. Hysteretic buck converter having dynamic thresholds
US8212491B2 (en) * 2008-07-25 2012-07-03 Cirrus Logic, Inc. Switching power converter control with triac-based leading edge dimmer compatibility
US8279628B2 (en) 2008-07-25 2012-10-02 Cirrus Logic, Inc. Audible noise suppression in a resonant switching power converter
US8344707B2 (en) * 2008-07-25 2013-01-01 Cirrus Logic, Inc. Current sensing in a switching power converter
US8487546B2 (en) * 2008-08-29 2013-07-16 Cirrus Logic, Inc. LED lighting system with accurate current control
US8222872B1 (en) 2008-09-30 2012-07-17 Cirrus Logic, Inc. Switching power converter with selectable mode auxiliary power supply
US8179110B2 (en) * 2008-09-30 2012-05-15 Cirrus Logic Inc. Adjustable constant current source with continuous conduction mode (“CCM”) and discontinuous conduction mode (“DCM”) operation
US8288954B2 (en) * 2008-12-07 2012-10-16 Cirrus Logic, Inc. Primary-side based control of secondary-side current for a transformer
US8299722B2 (en) 2008-12-12 2012-10-30 Cirrus Logic, Inc. Time division light output sensing and brightness adjustment for different spectra of light emitting diodes
US8362707B2 (en) * 2008-12-12 2013-01-29 Cirrus Logic, Inc. Light emitting diode based lighting system with time division ambient light feedback response
WO2010068223A1 (en) * 2008-12-13 2010-06-17 Hewlett-Packard Development Company, L.P. Systems and methods for scaling a signal in a power factor correction circuit
US8723498B2 (en) * 2008-12-19 2014-05-13 Hewlett-Packard Development Company, L.P. Systems and methods of increasing power measurement accuracy for power factor correction
US7994863B2 (en) * 2008-12-31 2011-08-09 Cirrus Logic, Inc. Electronic system having common mode voltage range enhancement
US8482223B2 (en) * 2009-04-30 2013-07-09 Cirrus Logic, Inc. Calibration of lamps
US8198874B2 (en) * 2009-06-30 2012-06-12 Cirrus Logic, Inc. Switching power converter with current sensing transformer auxiliary power supply
US8212493B2 (en) 2009-06-30 2012-07-03 Cirrus Logic, Inc. Low energy transfer mode for auxiliary power supply operation in a cascaded switching power converter
US8963535B1 (en) 2009-06-30 2015-02-24 Cirrus Logic, Inc. Switch controlled current sensing using a hall effect sensor
US8248145B2 (en) * 2009-06-30 2012-08-21 Cirrus Logic, Inc. Cascode configured switching using at least one low breakdown voltage internal, integrated circuit switch to control at least one high breakdown voltage external switch
US9155174B2 (en) 2009-09-30 2015-10-06 Cirrus Logic, Inc. Phase control dimming compatible lighting systems
US9178415B1 (en) 2009-10-15 2015-11-03 Cirrus Logic, Inc. Inductor over-current protection using a volt-second value representing an input voltage to a switching power converter
US8487591B1 (en) 2009-12-31 2013-07-16 Cirrus Logic, Inc. Power control system with power drop out immunity and uncompromised startup time
US8654483B2 (en) * 2009-11-09 2014-02-18 Cirrus Logic, Inc. Power system having voltage-based monitoring for over current protection
US8098503B2 (en) 2010-02-09 2012-01-17 Power Integrations, Inc. Method and apparatus to control a power converter having a low loop bandwidth
US8964413B2 (en) * 2010-04-22 2015-02-24 Flextronics Ap, Llc Two stage resonant converter enabling soft-switching in an isolated stage
US8912781B2 (en) 2010-07-30 2014-12-16 Cirrus Logic, Inc. Integrated circuit switching power supply controller with selectable buck mode operation
US8866452B1 (en) 2010-08-11 2014-10-21 Cirrus Logic, Inc. Variable minimum input voltage based switching in an electronic power control system
US9510401B1 (en) 2010-08-24 2016-11-29 Cirrus Logic, Inc. Reduced standby power in an electronic power control system
JP2012209052A (en) 2011-03-29 2012-10-25 Toshiba Lighting & Technology Corp Illumination apparatus
CN103583082B (en) 2011-06-03 2016-11-02 皇家飞利浦有限公司 For controlling method and apparatus and the power conversion equipment of switching power converter
CN103636109B (en) 2011-06-03 2016-08-17 塞瑞斯逻辑公司 For operating method and apparatus and the electric power distribution system of switched power transducer
US8779678B2 (en) 2011-08-23 2014-07-15 Dudley Allan ROBERTS Segmented electronic arc lamp ballast
CN104145412B (en) 2011-12-14 2016-12-21 塞瑞斯逻辑公司 Self-adaptive current for docking with dimmer controls timing and response current controls
CN102624214B (en) * 2012-04-10 2014-07-09 绍兴恒力特微电子有限公司 Circuit and method for controlling constant current of high-power-factor buck-boost switch converter
US9520794B2 (en) 2012-07-25 2016-12-13 Philips Lighting Holding B.V Acceleration of output energy provision for a load during start-up of a switching power converter
WO2014138629A1 (en) 2013-03-07 2014-09-12 Cirrus Logic, Inc. Utilizing secondary-side conduction time parameters of a switching power converter to provide energy to a load
US9735671B2 (en) 2013-05-17 2017-08-15 Cirrus Logic, Inc. Charge pump-based drive circuitry for bipolar junction transistor (BJT)-based power supply
US9253833B2 (en) 2013-05-17 2016-02-02 Cirrus Logic, Inc. Single pin control of bipolar junction transistor (BJT)-based power stage
WO2015017315A1 (en) 2013-07-29 2015-02-05 Cirrus Logic, Inc. Compensating for a reverse recovery time period of a bipolar junction transistor (bjt) in switch-mode operation of a light-emitting diode (led)-based bulb
US9496855B2 (en) 2013-07-29 2016-11-15 Cirrus Logic, Inc. Two terminal drive of bipolar junction transistor (BJT) of a light emitting diode (LED)-based bulb
US9214862B2 (en) 2014-04-17 2015-12-15 Philips International, B.V. Systems and methods for valley switching in a switching power converter
CN104199505B (en) * 2014-08-21 2016-07-06 康佳集团股份有限公司 A kind of Overpower compensating circuit and PFC Overpower compensating circuit structure
WO2016061815A1 (en) * 2014-10-24 2016-04-28 Texas Instruments Incorporated Adaptive controller for voltage converter
US9325236B1 (en) 2014-11-12 2016-04-26 Koninklijke Philips N.V. Controlling power factor in a switching power converter operating in discontinuous conduction mode
CN104578729B (en) * 2014-12-22 2017-03-29 广州金升阳科技有限公司 A kind of input filter method and the AC/DC switch converters using the method
US9504118B2 (en) 2015-02-17 2016-11-22 Cirrus Logic, Inc. Resistance measurement of a resistor in a bipolar junction transistor (BJT)-based power stage
US9603206B2 (en) 2015-02-27 2017-03-21 Cirrus Logic, Inc. Detection and control mechanism for tail current in a bipolar junction transistor (BJT)-based power stage
US9609701B2 (en) 2015-02-27 2017-03-28 Cirrus Logic, Inc. Switch-mode drive sensing of reverse recovery in bipolar junction transistor (BJT)-based power converters
AT15949U1 (en) * 2017-04-21 2018-10-15 Tridonic Gmbh & Co Kg PFC circuit
US11206743B2 (en) 2019-07-25 2021-12-21 Emerson Climate Technolgies, Inc. Electronics enclosure with heat-transfer element

Citations (13)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4683529A (en) 1986-11-12 1987-07-28 Zytec Corporation Switching power supply with automatic power factor correction
US5495149A (en) * 1993-05-20 1996-02-27 Matsushita Electric Works, Ltd. Power supply
US5757166A (en) * 1995-11-30 1998-05-26 Motorola, Inc. Power factor correction controlled boost converter with an improved zero current detection circuit for operation under high input voltage conditions
US5867379A (en) * 1995-01-12 1999-02-02 University Of Colorado Non-linear carrier controllers for high power factor rectification
US5872430A (en) * 1996-08-14 1999-02-16 Motorola Inc. Single switch electronic ballast with low in-rush current
US5912549A (en) * 1997-08-01 1999-06-15 Lucent Technologies Inc. Current mode controller for continuous conduction mode power factor correction circuit and method of operation thereof
US5925986A (en) * 1996-05-09 1999-07-20 Pacific Scientific Company Method and apparatus for controlling power delivered to a fluorescent lamp
US5986901A (en) * 1998-07-09 1999-11-16 Matsushita Electric Works R&D Laboratory, Inc. Power factor correction circuit for a power supply
US5991172A (en) * 1996-06-21 1999-11-23 Delta Electronics, Inc. AC/DC flyback converter with improved power factor and reduced switching loss
US6043633A (en) * 1998-06-05 2000-03-28 Systel Development & Industries Power factor correction method and apparatus
US6128205A (en) * 1999-05-07 2000-10-03 Philips Electronics North America Corporation Power factor correction with reduced total harmonic distortion
US6141230A (en) * 1998-07-13 2000-10-31 Broadband Telcom Power, Inc. Valley-fill power factor correction circuit
US6222746B1 (en) * 1998-02-09 2001-04-24 Samsung Electronics Co., Ltd. Power supply device and method with a power factor correction circuit

Patent Citations (13)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4683529A (en) 1986-11-12 1987-07-28 Zytec Corporation Switching power supply with automatic power factor correction
US5495149A (en) * 1993-05-20 1996-02-27 Matsushita Electric Works, Ltd. Power supply
US5867379A (en) * 1995-01-12 1999-02-02 University Of Colorado Non-linear carrier controllers for high power factor rectification
US5757166A (en) * 1995-11-30 1998-05-26 Motorola, Inc. Power factor correction controlled boost converter with an improved zero current detection circuit for operation under high input voltage conditions
US5925986A (en) * 1996-05-09 1999-07-20 Pacific Scientific Company Method and apparatus for controlling power delivered to a fluorescent lamp
US5991172A (en) * 1996-06-21 1999-11-23 Delta Electronics, Inc. AC/DC flyback converter with improved power factor and reduced switching loss
US5872430A (en) * 1996-08-14 1999-02-16 Motorola Inc. Single switch electronic ballast with low in-rush current
US5912549A (en) * 1997-08-01 1999-06-15 Lucent Technologies Inc. Current mode controller for continuous conduction mode power factor correction circuit and method of operation thereof
US6222746B1 (en) * 1998-02-09 2001-04-24 Samsung Electronics Co., Ltd. Power supply device and method with a power factor correction circuit
US6043633A (en) * 1998-06-05 2000-03-28 Systel Development & Industries Power factor correction method and apparatus
US5986901A (en) * 1998-07-09 1999-11-16 Matsushita Electric Works R&D Laboratory, Inc. Power factor correction circuit for a power supply
US6141230A (en) * 1998-07-13 2000-10-31 Broadband Telcom Power, Inc. Valley-fill power factor correction circuit
US6128205A (en) * 1999-05-07 2000-10-03 Philips Electronics North America Corporation Power factor correction with reduced total harmonic distortion

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
Motorola Analog IC Device Data "Power Factor Controllers" pp. 1-16 Order this document by MC34262/D.

Cited By (23)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US8154269B2 (en) * 2008-08-21 2012-04-10 Leadtrend Technology Corporation Control apparatus and control method for a power factor correction power converter
US20100046262A1 (en) * 2008-08-21 2010-02-25 Leadtrend Technology Corporation Control Apparatus and Control Method for a Power Factor Correction Power Converter
US8593127B2 (en) 2008-09-15 2013-11-26 Power Integrations, Inc. Method and apparatus to reduce line current harmonics from a power supply
US7923973B2 (en) 2008-09-15 2011-04-12 Power Integrations, Inc. Method and apparatus to reduce line current harmonics from a power supply
US20110157943A1 (en) * 2008-09-15 2011-06-30 Power Integrations, Inc. Method and apparatus to reduce line current harmonics from a power supply
US8207723B2 (en) 2008-09-15 2012-06-26 Power Integrations, Inc. Method and apparatus to reduce line current harmonics from a power supply
US8487601B2 (en) 2008-11-07 2013-07-16 Power Intergrations, Inc. Method and apparatus to control a power factor correction circuit
US9116538B2 (en) 2008-11-07 2015-08-25 Power Integrations, Inc. Method and apparatus to increase efficiency in a power factor correction circuit
US8004262B2 (en) 2008-11-07 2011-08-23 Power Integrations, Inc. Method and apparatus to control a power factor correction circuit
US9618955B2 (en) 2008-11-07 2017-04-11 Power Integrations, Inc. Method and apparatus to increase efficiency in a power factor correction circuit
US20100118571A1 (en) * 2008-11-07 2010-05-13 Power Integrations, Inc. Method and apparatus to control a power factor correction circuit
US8525493B2 (en) 2008-11-07 2013-09-03 Power Integrations, Inc. Method and apparatus to increase efficiency in a power factor correction circuit
US20100118573A1 (en) * 2008-11-07 2010-05-13 Power Integrations, Inc. Method and apparatus to increase efficiency in a power factor correction circuit
US8040114B2 (en) 2008-11-07 2011-10-18 Power Integrations, Inc. Method and apparatus to increase efficiency in a power factor correction circuit
US8749212B2 (en) 2008-11-07 2014-06-10 Power Integrations, Inc. Method and apparatus to control a power factor correction circuit
US8467209B2 (en) 2010-07-27 2013-06-18 Stmicroelectronics S.R.L. Control device of a switching power supply
US10439508B2 (en) 2010-07-27 2019-10-08 Stmicroelectronics S.R.L. Control device of a switching power supply
US10461658B2 (en) 2010-07-27 2019-10-29 Stmicroelectronics S.R.L. Control device of a switching power supply
US9154030B2 (en) 2012-01-26 2015-10-06 Stmicroelectronics S.R.L. Control device of a switching power supply
US9461558B2 (en) 2012-01-26 2016-10-04 Stmicroelectronics S.R.L. Control device of a switching power supply
US20140132191A1 (en) * 2012-11-15 2014-05-15 Samsung Electro-Mechanics Co., Ltd. Power factor correction apparatus, power supplying apparatus and motor driving apparatus having the same
US9148062B2 (en) * 2012-11-15 2015-09-29 Samsung Electro-Mechanics Co., Ltd. Power factor correction apparatus, power supplying apparatus and motor driving apparatus having the same
US9705412B2 (en) 2015-02-26 2017-07-11 Stmicroelectronics S.R.L. Pulsed feedback switching converter

Also Published As

Publication number Publication date
JP3406897B2 (en) 2003-05-19
JP2001057781A (en) 2001-02-27
US6259614B1 (en) 2001-07-10
DE10032846A1 (en) 2001-01-25

Similar Documents

Publication Publication Date Title
USRE40016E1 (en) Power factor correction control circuit
US6946819B2 (en) Device for the correction of the power factor in power supply units with forced switching operating in transition mode
US11005361B2 (en) Control circuit and method of a switching power supply
US7064527B2 (en) Transition mode operating device for the correction of the power factor in switching power supply units
US6049473A (en) Harmonic-injection control technique for three-phase, discontinuous-conduction-mode, high-power-factor boost rectifiers with improved line-transient response
US5565761A (en) Synchronous switching cascade connected offline PFC-PWM combination power converter controller
US7116090B1 (en) Switching control circuit for discontinuous mode PFC converters
US5903138A (en) Two-stage switching regulator having low power modes responsive to load power consumption
US6531854B2 (en) Power factor correction circuit arrangement
US7307405B2 (en) Transition mode operating device for the correction of the power factor in switching power supply units
CN100403629C (en) Power factor correction device for switching power supply
US5726845A (en) Short circuit protection for power factor correction circuit
US10241322B2 (en) Device and method for quasi-resonant-mode voltage control of a switching converter
US8270190B2 (en) Fixed-off-time power factor correction controller
US5982639A (en) Two switch off-line switching converter
US20020196006A1 (en) Volt-second balanced PFCPWM power converter
US6166924A (en) Device and method of supplying energy from an ac source in an ac to dc converter
JPH09205766A (en) Power factor compensating circuit
JPH07203685A (en) Power factor correction circuit
EP0782782B1 (en) Power factor corrected electrical power converter
US20110037443A1 (en) Parallel connected pfc converter
US10581321B1 (en) Flyback converter with multiplier signal control circuit and method
JP4051899B2 (en) Power supply circuit and control method of power supply circuit
US6717826B2 (en) Method to reduce bus voltage stress in a single-stage single switch power factor correction circuit
JP2000116133A (en) Waveform shaping circuit

Legal Events

Date Code Title Description
REMI Maintenance fee reminder mailed
FPAY Fee payment

Year of fee payment: 8

SULP Surcharge for late payment

Year of fee payment: 7

FPAY Fee payment

Year of fee payment: 12

AS Assignment

Owner name: INFINEON TECHNOLOGIES AMERICAS CORP., CALIFORNIA

Free format text: CHANGE OF NAME;ASSIGNOR:INTERNATIONAL RECTIFIER CORPORATION;REEL/FRAME:046612/0968

Effective date: 20151001