WO1990004895A2 - Information coding process - Google Patents

Abstract

According to known information coding processes, channels are condensed by frequency or time multiplexing, at a high cost and requiring a large bandwidth. According to the invention, serially arranged code elements are individually arranged in parallel, then united in a single code word. The safety of transmission is ensured by converting the information into pulse-width modulated pulses and by coding such pulses as half-periods or as periods which are then transmitted in an uninterrupted sequence of positive and negative half-periods.

Description

Information encoding method.

The present invention relates to a method for coding information. Et al it shows how to achieve digital and / or analog coding of information from one, two or more channels and / or a frequency or bandwidth reduction and / or an increase in transmission security.

 Up to now, frequency and time-division multiplexing methods such as e.g. the carrier frequency technology and the pulse code modulation are known. A disadvantage of these methods is that they require large bandwidths and a lot of effort.

 The object of the present invention is to transmit the information of one, two or more channels with less bandwidth and to transmit the information of two or more channels over a channel with less bandwidth than would be required for the sum of the individual channels. This is done by synchronously or Code elements of the different channels arranged in quasi-synchronous order are to be arranged in parallel, and all are combined and transmitted to form one code word. This is done by e.g. the PAM pulses in PDM, PPM and PFM pulses in sinusoidal half periods. Period impulses or Code elements are converted that are sent in an uninterrupted sequence of positive and negative half-periods. The half period or Period duration is a measure of the PDM-PPM and PFM impulses.

The invention can e.g. are used to combine telex, teletex, fax, digital voice data channels. The invention can also be used to advantage in the case of shared connections and selector switches.

Furthermore, the invention shows possibilities of advantageous coding of new television techniques to improve C-MAC, D-MAC, D2-MAC etc. Furthermore, it can also be used in the further development of the HDTV method. All of these new television methods are very limited in their possibilities due to a lack of bandwidth. Furthermore, the invention discloses an advantageous phase coding of the color tone in television. It is not the phase shift which is coded in the alternating current and which is a measure of the hue that is transmitted, but rather the phase shift of the sample values which is subsequently transmitted into the period of the coding alternating current, the amplitude encoding the saturation vector.

In addition, the invention shows applications for duplex traffic with an alternating current of an equenzrequency. This is based on the principle of adding two alternating currents that are 90 degrees out of phase, in which the amplitudes of the half-waves represent the information and then do not cancel each other out in oncoming traffic. In addition, applications for double quadrature amplitude modulation are shown, in which the 4 encoding alternating currents are summed up twice and which have a phase position of 0.90, 90.180 degrees and a phase position of 45 and 135 degrees with the second summation.

My patents and published documents also apply as prior art: patents US 4,794,621, 4,675,721, 4,731,798 Canada 1214277, European laid-open documents 0110427, 0197529, 0239959, 0284019, German disclosures DE 3629706.2, 3514664.8, 3719670.7, 3802088.2, 3805263.6.

The invention is explained in more detail below with reference to drawings. These represent:

Fig.1 Principle of a code division multiplex arrangement

 Fig. 2 Previous generation of phase jumps e.g. in the

 4 psr

 Fig. 3 to 8 and 83 generation of bubble jumps

 Fig. 9 Generation of amplitude levels

Fig. 10,11 and 13 representation of a double QAM and vector diagram of a higher-quality coding

 Fig. 14 Vector diagram of a double QAM

 Fig. 16 Arrangement of the coding points in the case of multi-value coding by means of amplitude variables and phase position

 Fig. 15 Overview for the generation of phase and amplitude stages

 Fig. 17 Generation of phase jumps

 Fig. 18, 19, 20, 21, 24, 28, 79 code multiplex examples

Fig. 22,23 Overview of a television transmitter and receiver Fig. 25, 26, 27 duplex traffic via lines and radio with only one alternating current with phase adjustment

Fig. 29 Compensation of overlaps

 Fig. 30,31,32 generation and conversion of PDM pulses in

 Half-period pulses

 33 to 38 generation and conversion of PDM pulses into an alternating current

39 to 44 encodings according to the invention for television

Fig. 45,46,62,63 double binary and double duobinary arrangement of code elements

Fig. 47,48,49 circuit overviews for television

50 to 55 encodings of color television signals

Fig. 56,57,58 Multiple use of transmission paths of PDM-coded signals

 Fig. 59.60 Evaluation of phase-modulated signals

 Fig. 64 Diagram of frequency modulated dependence

Vibration from the amplitude and frequency of the modulation vibration

Fig. 65 Coding plan for color television

Fig. 66 narrowband digital code

Fig. 67 Scheme for television phase coding

Fig. 68,69 A phase encoding for color television signals

Fig. 70, 71 Serial arrangement of television signals

Fig.72 principle arrangement for the transmission of television signals, phase-coded.

Fig. 73, 74 pulse duration modulation circuit

 Fig. 75.76 Principle of multiple transmission of pulse duration modulated signals over a current path

Fig.77.78 Digital coding of color television signals and circuit for transmission

Fig. 80.8.1 Half-period durations for phase encodings

Fig. 82 Circuit diagram for the accommodation of an information channel between 2 television channels

A simple way of realizing phase jumps is described in FIGS. 3, 4, 5, 6 and 7 this is explained in more detail. Rectangular pulses with a frequency of 1 MHz are switched on on the transmitting side S. Is, as shown in Fig.3c, in the transmission path

Low pass TP 5.5 MHz switched on, one almost receives a rectangular pulse at the receiver E. As shown in Fig.

3b drawn in, a low-pass filter TP of 3.5 MHz switched on, the vertical slope is no longer / is present, but if, as shown in FIG. 3a, the low-pass filter is reduced to 1.5 MHz, the receiver E receives a sinusoidal alternating current with the Period duration of the rectangular period. So since the period duration does not change compared to the rectangular pulse, the phase can also be changed by changing the period end periods of the rectangular pulses. Change frequency of the sinusoidal alternating current shown in Fig.3a. Since such a change always occurs at the zero crossing, there is a continuous change and hardly any harmonics are generated, i.e. the transmission is more narrow-band than with the previously used phase keyings. In the receiving station, the change in the period can then also be provided as a measure of the phase shift. Such an evaluation circuit will be described later.

4 shows rectangular pulses with different period durations T = f, T = f1 and T = f2. According to an analog arrangement according to FIG. 3a, a sinusoidal alternating current with the period durations T = 1 / f, T would be received on the receiving side = 1 / f1, T = 1 / f2. Since the frequency sequence of the alternating current decreases or increases in the case of phase jumps, the frequency change corresponds to a phase jump. This is clearly shown in FIG. 2, which represents a \ phase keying of a conventional type. This shows that with every phase change there is a frequency change, but not in a continuous manner. It is therefore difficult to determine the size of the phase jump from the period on the receiving side. In order to keep the frequency changes and thus also the frequency band small, each phase jump can be broken down into stages. This is shown schematically in FIG. In / this is T / 2 the half period of a pulse and corresponds to 180 °. This angle is divided into 36 steps of 5 degrees each. Should a phase jump of 40 degrees occurs, the half period T / 2 is shortened 4 times by 5 degrees and of course the other half period as well. The half period compared to the reference pulse is then T1 / 2. After the phase jump you can either leave this frequency or switch back to the frequency T / 2 by providing a phase jump of 5 degrees in the opposite direction. Compared to the reference phase, there would still be a phase shift of 30 degrees. 6, the times of the reference phase and 4 times the periods of the periods shortened by 2x5 degrees are shown 4 times. A comparison after the 4th period shows the difference of 40 degrees compared to the reference phase.

7 shows a circuit of an embodiment of the invention. It is assumed that the periodendans are subdivided into 72 levels, namely with phase jump levels of 5 degrees. 10 measuring pulses are to be assigned to each stage, for example 72x10 = 720 measuring pulses for the period and 360 measuring pulses for the half-period. On the transmission side, only the half periods need to be coded. The second half period is then controlled via the encoder Cod. If phase jump steps of 5 degrees are provided, 350 measuring pulses are required for the half-period if the change is to be leading and 370 for a lagging phase change. Counter Z in FIG. 7 must therefore have at least 370 outputs. The mass pulse frequency therefore depends on the coding frequency. In the example of the ϊig 7, the control alternating current for the measuring pulses is generated in the oscillator Osc. You can use it to control the counter directly via gate G1, or you can also generate pulses by means of a Schmitt trigger or another circuit and then switch counter Z with these pulses. You can also change the pulse duration by changing the oscillator frequency. The output Z2 on the counter Z is assumed to mark 370 measuring pulses, ie the lagging phase shift, then the encoder

Cod via g2 such a potential at one input of the

Gate G2 placed that then when reaching the counter output Z 2, then z. the same potential at the other input of G2, the potential at the output of G2 changes, e.g. from h to 1. In the electronic relay ER, this has the result that positive potential + is applied to output J. Via the connection A, the Codie rer Cod is connected to the electronic relay ER. The next time the counter Z to Z2 overflows, connection A controls the ER so that output minus potential - is applied to output J. Bipolar square-wave pulses can therefore be taken from the output of ER. One could generate unipolar square-wave pulses in exactly the same way. This process is repeated as long as the encoder applies potential to G2. If, for example, 5 phase stages are provided for a phase jump, the counter Z is switched 10 times to Z2. At output Z2, the counter is switched back via gate G4, R. It is possible to set the pulse duration, the number of stages and the size of the stages by changing the number of outputs on counter Z and / or by changing the oscillator frequency These variants are controlled via the encoder Cod. The oscillation frequency can be switched via fA, the number of stages and, if necessary, the phase angle change and the stage size and the amplitudes of the rectangular pulses J via A via connections g2, g3,. In the example, 2 sizes + / (A) +, - / (A) - are provided. The rectangular pulses J are then connected to a low-pass filter analogous to FIG. 3 and given via a transformer U, for example on the transmission path, possibly with the interposition of a filter Fi.

Starting potential must still be applied to gate G1 via B so that the oscillator pulses take effect. With this arrangement, the following codings are possible: a leading one, a trailing one, no phase shift. These can also be done in stages. The phase difference or the reference phase can be used. In addition, an amplitude coding can optionally be provided in stages. Another possibility is to encode the positive or negative pulse. Half wave. The number of square-wave pulses is another code means. You can also filter out a harmonic of the square-wave pulses. If this occurs, for example, with the 3rd harmonic, there are 3 periods contained in a plus / minus pulse. In these 3 periods, the phase shifts are included even if the pulse duration is changed.

 In a wide variety of circuits, such as Quadrature amplitude modulation (QAM) requires AC currents that are 90 degrees out of phase with each other. 8 shows a maintenance principle for generating such phase-shifted alternating currents of the same frequency. Analogously to FIG. 7, the counter Z is controlled by an alternating current which is generated in the oscillator Osz and is guided via the gate G, at the other input of which there is a starting potential B. In the example, 4 square-wave pulses are to be generated which act against one another If the counter Z has 100 outputs, then at 25.50., 75. and

 100. Output electronic relay ER1 to ER4 to be switched on analogously to the ER relay in Fig. 7. With these electronic relays, as already described in FIG. 7,

Rectangular pulses are generated. There are still means in the ER relays that always reverse the potential in the case of bipolar rectangular pulses and remove the potential in the case of unipolar rectangular pulses during a run. The rectangular pulses are then designated J in FIG.

sent via the filters Fi1 to Fi4. The resulting alternating current has a phase shift of 90 degrees compared to that generated by the next output. Instead of phase-shifting alternating currents, the outputs can also be switched by 90

 Degrees of phase-shifted decreases, e.g. Control PAM samples.

 A filter FiO is also connected to the electronic relay ER1, e.g. only passes the 3rd harmonic of the square pulse, so that here you get 3 times the frequency of the square pulses. The phase shift is then transferred to the 3rd harmonic.

With Fig.7 you can also generate different amplitude levels at the same time. Only 2 are identified in the circuit. In FIG. 9, another possibility is to generate different amplitude levels. The alternating current generated, for example, in FIG. 7 is fed to a limiter in which the control pulses are generated. The characteristic states are via the connection code fed, which make a switch to the amplitude size determined by the code and that in the encoder Cod. The switch to a different amplitude size always takes place during the Hull passage. The magnitude of the amplitudes is determined by the resistors R1 to R4, which are arranged in AC circuits. Electronic relays I to IVes, which are controlled by the encoder Cod, switch on the various resistors in the AC circuits. At output A you get 4 different amplitudes.

It is also known to provide information through the half waves. To code periods of an alternating current; in the case of a binary code, the characteristic states are large and small amplitude values. If two such alternating coding currents of the same frequency are phase-shifted and added by 90 degrees, they can be transmitted with an alternating current of the same frequency. 10a, b are the channels K1 and K2, which are encoded by the feriodes as code elements with the characteristic states of large amplitude value = 1 and small amplitude value = 0. If one phase is shifted by 90 degrees against the other, they can be added. Their vector diagram is shown in FIG. The channel. K1 has the vector K1 (u) and the channel K2 has the vector k2 (v). The two characteristic states of the two alternating currents are designated u1 / uo and v1 / vo. If both are added together, the four sum vectors I, IV and II, III are obtained. You can see that vectors II and III are no longer on the 45 degree line. This makes evaluation a little more difficult. For the evaluation of the binary signals, 4 options are sufficient, all of which are at 45 degrees. Dinie can lay, designated in Fig.11 with (ll) and (IIl). The four possibilities are shown in FIG. 13, 00, 11, 10, 01. If all 4 possibilities are on the 45 degree vector, as shown in Fig. 11, they can be coded by 4 different large amplitudes, ie with a sinusoidal alternating current. Such a possibility is shown in FIG. To transmit binary signals from 2 channels, a multi-value quaternary code such as the 4 PSK or 4 QAM is sufficient. These codes are spread over a period. In Fig. 9 the positive and negative half-wave are of equal size, it is then the over a DC current freedom. The poositive and negative half-wave can be used as an additional criterion. You can then distribute the 4 amplitude characteristics, 2 on the positive and 2 on the negative half-wave. These can have the same size, for example in Fig. 11, I + IV

for the positive and negative half wave. So that this coding alternating current is always above the interference level, the coding alternating current must always have a certain magnitude, e.g. as in Fig. 11 (III). The amplitude size IV will then be increased somewhat.

 A reduction: from e.g. binary-eroded alternating currents with the half-waves respectively Periods as code elements are already known. The prerequisites for this are phase shifts in the sampling. The present invention shows a further possibility of reducing the frequency, in particular binary-coded information. In Fig. 1, a channel K is recorded with a binary code 1, 0,1,1, ... If the frequency of the channel is to be reduced to 2 channels with half the frequency, then 2 serial binary values of the channel must be arranged. K can be distributed in parallel to channels Kv1 and Kv2, e.g. the 4 values 1, 0.1, 1 of the channel K, the value 1 on Kv1, the value 0 on Kv2, the value 1 again

Kv1 and the wider value 1 on Kv2. You can always save a value, or you can transfer the values at different times. This must be taken into account in the evaluation. A simultaneous transmission of 2 channels has already been shown in FIGS. 11 and 13. As can be seen from FIG. 13, 4 combinations are possible.

10 shows 4 coding alternating currents K1-K4 with the code elements period and the characteristic states of large and small amplitude values of the same frequency. If you want to transmit all 4 on the basis of the QAM, these must have the following phases, K1 = OGrad, K2 = 90 degrees, K3 = 90 degrees and K4 = 180 degrees. K1 / K2 and K3 / K4 are combined to form a coding alternating current in accordance with FIG. 9 and added. The vector diagram for this is shown in FIG. 14. You can see that 16 combinations are possible. It can also be seen from this that only 4 values lie on the 45 degree vector. When evaluating, the leading values must be used for the other values resp. lagging phase shift are taken into account. The phase-shifted alternating currents are generated in an arrangement as shown in FIG. 8, and 2 arrangements are supplied according to FIG. 9, these alternating currents being phase-shifted with respect to one another by 90 degrees.

 A total alternating current and simple coding alternating current can also be added, provided that a 90 degree phase shift is required. This creates 8 possible combinations.

4 channels can also be transmitted in a coding-multiplexed manner, as shown in FIG. 1 (Kv1, Kv2, Kv3, Kv4). Then 16 combinations are necessary. You can also provide known encodings, such as. B. the 16 PSK, the 16 QAM, the 8 PSK. A period is required for coding in each case if phase shifts are provided according to the present invention. Instead of the closely related characteristic states in the double QAM according to Fig. 14, one can also carry out any coding. In Fig. 16 the coding is carried out by 30 degree phase differences and by 3 and 4 amplitude levels. If you still want greater security, you can still divide the 4 amplitude levels BPh. Steps can still be accommodated on the zero line. So you can provide each half-wave for such coding. However, if you want to carry out a transmission via wired transmission paths, it is advisable to transmit the negative half-wave with the same coding, so that one is free of direct current. The same method can be used to downsize. In Fig.l the channel should only be transmitted with the quarter frequency. In each case 4 binary elements 1 and 0 arranged in series are arranged in parallel as provided in FIGS. 1a, b. The values 1,0,1,1 of the channel K are then divided in parallel between the channel Kvl "1", channel Kv2 "0", channel Kv3 "1" and channel Kv4 "1". The predetermined coding point is then determined in the encoder for the respective combination and transmitted to the phase and amplitude of the coding alternating current. The phase is defined in FIG. 7, if necessary, one can also use this to set the Am encode plitude, and in Figure 9 you can then encode the required amplitudes. The overview for this is shown in FIG. In the encoder code, the coding point is determined based on the combination of four. The phase encoder generates the half waves. Periods with the appropriate phase and the amplitude encoder generates the associated amplitudes. A phase encoder can look analogous to Figure 7 and an amplitude encoder analogous to Figure 9. A phase jump always means a change in the period. This change, i.e. frequency change, cannot be maintained with any further phase change, or you can change the next period. Switch half period back to the original frequency. Since in the latter case the alternating current has a different phase, a reference phase is required for the evaluation. As can be seen in FIG. 4, any phase can be maintained with the circuit of FIG , d. H. maintain the frequency that arose during the phase change. The phase changes are always made in the present case at the zero crossing. A reference phase BPh can be seen in FIG. 16, from which a phase shift is carried out 2x30 degrees ahead and behind.

16 shows a generation of the phase jumps of FIG. 16 according to the principle of FIG. 7. The angle of 360 degrees is characterized by 3600 pulses. If there is only an amplitude change with the reference phase, the counter is always from 0 switched through to 360 degrees. The control takes place via the encoder code, which was already described in Fig. 7. The change in amplitude takes place as shown in FIG. 7 or in FIG. 9. If the phase jump Ph1 is to take place in FIG. 16, then switching to the output 195 has to be carried out every half cycle if a DC current freedom is required. A reference phase is not necessary for the evaluation because, as long as there is no further phase change, the clear phase is determined by the period. If the coding is on the vector Ph3, the period is 330 degrees, ie there is always a changeover at the output 165 always related to the period. If, for example, the phase shift was related to the half-period in the latter case, a switch-back would have to take place at output 150. Other methods of generating phase jumps can be used exactly as well.

 As is known, the phase jumps are evaluated by measuring the period durations by means of an excessive control speed of counter elements, e.g. in European patent application 86104693.6.

A reference phase is required for each evaluation of FIG. 14. The amplitude points 1 to 4 are immediately on the reference phase, while the other 12 coding points are arranged to lead and lag the reference phase. The signals are assumed to be those of a television system.

The reference phase is then determined during the blanking time and control signals are simultaneously transmitted. Only the amplitude values on the reference phase are used. From the transmission path ÜW, the signals are fed to the input set EST (Fig. 12). Once they go to a delimiter B and once to a code evaluation CA. In the limiter, the positive and negative half-waves are converted to Jp and Jn pulses. In the comparison device VE, the phase of the

Transmission path coming pulses compared with a reference phase pulse JBn. FIG. 12a shows the leading and the reference phase pulse Jv, Jn, JB, which are compared with the reference phase pulse JBn determined from a coding. The 3 possible phase values leading or reference phase are given for code evaluation. The amplitude values are determined in this and, in conjunction with the leading or reference phase, the coding points are then determined and transmitted via S for further use. The coding of the reference phase in the blanking time can, for example, be such that 4 times the point 2 and 4 times the point 4 are sent on the reference phase. The evaluation of these takes place in the reference phase evaluation BA. From this a reference phase pulse JBn is then given to the comparison device.

 Another embodiment of the invention is shown in FIG. The 5 channels K1 to K5 are intended to be code-multiplexed: Way will be transferred. The e.g.

 binary coded information of these 5 channels. is first stored in memory Sp. In Fig. 20 e.g. the steps of the binary characters are shown and already synchronized. To encode are 5 steps arranged in parallel respectively. Pulses S1,2,3, ... The steps of S1 are 1-1-0-1-0. 5 bits are required for coding these 64 combinations. In the example, these are coded with the amplitudes of the half-waves of an alternating current with the characteristic states of large and small amplitude values and with a leading and a lagging phase jump of 36 degrees, as shown in FIG. 19. The binary values are fed from the memory Sp in FIG. 18 to the encoder Cod and are converted into a corresponding code in the latter. In the decoder on the receiving side, the corresponding standing steps are assigned to the channels again according to the code.

FIG. 21 shows a further application of the invention for the coding and transmission of the signals in color television. The luminance signal is tapped at 6 MHz. This principle has already been disclosed in published patent application P 32 23 312. The colors red and blue should each be picked up with 1.2 Mnz, ie each red and blue tap hits 5 luminance taps. The luminance taps are designated l, ll, III, lV, V. These samples are coded with 8 bits, in the example binary coded. With tap III, the taps for red and blue must also be made. The red and blue samples are binary coded with 6 bits in the example. During the transmission of the 5 luminance samples, the code for the color samples red and blue is sent at the same time. With the tapping of red and blue one could begin with the transfer of the color and with the sampling I of the luminance s ignales. You can also save all 5 luminance samples and only start transmitting all television signals after the 5th sample. In Fig.21a are the binary codes of all signals to be transmitted are recorded. The 8 bits 1-8 of the luminance samples are arranged in parallel. The sound and other signals and the 6 bits of the blue signal are then arranged in series under 9.10 digital sound and other signals T + So, the 6 bits of the red signal and again the sound and other signals under 11.12. It is expedient if the luminance samples I to V are still stored at the transmitter and the color codes for red and blue are sent with the previous luminance samples, so that the receiver does not have to store the 5 luminance samples. Then only the red and blue samples have to be saved. The sound and other signals must also be stored and then sent to the loudspeaker at the same time as the picture. These signals can of course also be placed in the blanking time. In the example, 12 bits are required for the transmission of a luminance sample for the sound and other signal samples and for the color sample taking. An example of the coding of these 12 bits is shown in FIG. 21b. 5 half periods of an alternating current are provided for this. The binary code consists of code elements of the half-waves with the characteristic states of large and small amplitude values. In addition, a leading and lagging phase shift of 36 degrees is provided, so that one obtains 12 bits.

An overview of such a television transmitter is shown in FIG. The control element StO controls the TV camera FK also supplies the other control signals such as blanking and synchronization signals A + S. The red-green and blue signals are fed to the Y-matrix YM and red and blue at the same time to the color processing FA. At the same time, a capacitor K is provided which taps the luminance signal Y, the color signals r + b1 and the sound and other signals . At tap 3, a criterion for color processing is given via connection 3a. In this tap, the red and blue signals are tapped and both values are stored in capacitors C1 and C2. The FA is also fed a Y value from the Y matrix which is present at the third tap, so that the color difference signals ry and by er are obtained at tap 6a and 6b holds. -You can also only tap the color separation signals.- The sound and other signals are fed via 6c and 6d to the concentrator via the TSo module. All values are fed from the concentrator to a memory Sp. From the memory, the signals are fed to an analog / digital converter in a timely manner, for example as described in Fig. 21a. This is encoded in accordance with Fig. 21b. During the blanking period, a switchover to the concentrator K1 takes place via U. As a blanking criterion, the code word can be sent a few times with only zeros. Other signals So can also be sent during the blanking time. The beginning of a line can also be marked with a null code. While the line is through

the sequence and the number of half-waves given a synchronization. In the present code, a nominal frequency of 15 MHz is required. If you only want to use an amplitude code, 2 alternating currents with 18 MHz each are required, which could then be phase-shifted by 90 degrees and transmitted together. It is only a question of economy and safety which method is used here. In the example, the leading or lagging phase jump is determined by the period, so no reference phase is then required. Of course, multistage amplitude codes and / or phase codes can be used to reduce the frequency. For example, the PAM signal can be applied to the T input, which is then tapped off frequently within the 8 kHz time. There are numerous possibilities to use the tap 6c / 6d. A partial overview of a television receiver is shown in FIG. Via the HF oscillator and mixer and the

Amplifier V, the signals are fed to the demodulator DM. In this, for example, the signals as shown in FIG. 21b are recovered and fed to the decoder DC. The color signals are passed on in the sequence of the matrix Ma. The Y signal is also connected to this. At the output of the matrix, for example, the color difference signals RY.GY and BY are obtained, which, like UY, are sent to the television sets. The D ecoder DC then also supplies the blanking and synchronization signals AS, the sound and other signals. 24 shows an example in which the code for code multiplexing is obtained from several alternating currents. It represents a binary code in which the half-waves of the alternating currents serve as code elements and in which a large and a small amplitude value form the characteristic states . The characteristics to be transmitted consist of rectangular pulses with a frequency of 1000 Hz, as shown in FIG. 24b.

20 channels are to be transmitted code-multiplexed. For this, the half-waves of the alternating currents 1000, 1500, 2000,

2500 and 3000 Hz are provided. Of course, each channel can be supplied with multiple channels of low bit frequency in a time-division manner. The same number of bits could be achieved in exactly the same way with two alternating currents at 2000 Hz and another two alternating currents at 3000 Hz, each of which would have to be 90 degrees out of phase with respect to one another so that they could be added during transmission. It is already known how best the synchronization between the individual channels is established (instruction sheets of the DBP 4/6 year 79), and it will therefore not be discussed any further. In the same way you can also digitize the language. transmit several voice channels simultaneously.

In the case of amplitude coding, duplex operation can be carried out with the same alternating current. For this it is necessary that the countercoding alternating current is 90 degrees out of phase. This principle is shown in FIG. 25. The code can be digital, a binary code according to the patent DE 30 10 938 or else analog according to the Canadian patent 1 214 277. With half-waves as code elements, the frequency is 32 KHz for digital coding and 4 KHZ for analog coding. In Fig. 25, S1 is the microphone and E2 is the handset of one participant and S2 and E1 of the other participant. In S1 there is still an encoder in which the coding alternating current is obtained from the speech. The coding alternating current goes from S1 via a fork G, the connection resp. Connection line RL to fork G of the opposite party and to handset E1. In this there is also a decoder that recovers the speech from the coding alternating current. The coding alternating current from S1 is the synchronizing alternating current. From E1 this becomes branched off to S2 via a phase shifter at 90 degrees, in which it may be amplified. If S2 speaks, a coding alternating current that is 90 degrees out of phase is sent via G, RL, G to E2, decoded there and transmitted to the listener as speech. If, for example, there is a short spoken voice, an addition alternating current arises on the transmission path RL. An extinction is not caused. This principle can also be provided for duplex traffic in data transmission. Further related examples are disclosed in laid-open specification 3802088.

 This method can of course also be used for radio e.g. can be used for directional radio. An overview of this is recorded in Fig. 26. The transmission alternating current is also provided here as a coding alternating current. Pre-stage modulation is advantageously used. The transmission alternating current is generated in the oscillator 0sz1. The basic signal is converted into an alternating current digital code in the Amalog digital converter A1 / D1. It is even easier to provide an arrangement according to FIG. 7 as an oscillator and encoder. The electronic pelais is then controlled by the encoder in such a way that large and small rectangular pulses are present at the output J, which are then in the

Low pass TP can be formed into a sinusoidal alternating current. - The encoding alternating current then reaches the output stage Ε and the transmitting antenna via amplifiers (not shown). A branch circuit can also be provided in the output stage by phase-shifting the harmonics by 180 degrees, which are then fed back to the main current circuit for compensation. On the receiving side, the useful signals are fed to an amplifier V via a fixed tuning circuit and then switched on to the digital-to-analog converter D2 / A2. The analog signal is! Damn forwarded for example via a mediation. Via the amplifier V, the alternating transmission current is also branched off to a phase shifter of 90 degrees Ph and then switched on to the oscillator Osz2. The oscillator is synchronized with this. The transmitter is then operated in the opposite direction via the converter A3 / D3, the amplifier (not shown) and the output amplifier E. Receiver E1 is held exactly like receiver E2, only the phase shifter is not required. A phase shifter based on the principle of FIG. 7 is shown in FIG. 27. This also provides compensation for small frequency fluctuations. For this purpose, a counter Z is provided with 1000 outputs. During a half wave of the alternating transmission current, the counter runs through these 1000 outputs. The control pulses Js are generated in an oscillator, not shown. With a 90 degree phase shift, a half-wave encounters a phase shift of 45 degrees, which corresponds to 250 outputs. The transmission alternating current half-waves coming from the amplifier V are fed to a limiter, so that rectangular pulses Jp and Jn are produced at the output of the same. These pulses are connected to the control element St. The control pulses Js and the start indicator Be are also applied to this. The control element is switched so that only whole Jp resp. Jn impulses take effect on the counter. If the counter has reached the output 1000 during a pulse Jp, the gate Gll comes into the working position. A Jn pulse is connected to the gate G12 and, after the end of the Jp pulse, the potential is briefly switched on by the delay of the monostable element mG4.

G12 takes effect and applies potential to one output of G13, 1 potential has already been applied from Gll to the other input of G13. A potential change now occurs at the output of G13, the G16 at the output voltage, which means that G17 generates a switchback potential for / the counter.

Such potential is also applied to the gates G8, G9 and G10 that, in cooperation with the assigned outputs 1000, 999, 1001, they control one of the monostable elements mGl, mG2 or mG3. Since the Jp pulse controlled the counter up to 1000, the gates G9 and mG2 now took effect. If the counter is now controlled with the next Jn pulse on the output 250, then the gate G6 becomes effective, which controls the electronic relay ER, which generates a rectangular pulse according to FIG. 7, which is formed into a half-wave in the low pass. For the Jn pulse, the gates G15 G14 and the monostable element mG5 are arranged for the output marking. The monostable element mG2 holds e.g. to the exit 260. G6 then returns to the starting position. The electronic relay remains until the next marking of the output 250 in the this position. If only frequency 999 is reached due to a frequency fluctuation, then gate G8 is marked instead of G9 and mG1 and G5 are activated when output 249 is reached. If output 1001 is reached, G10 and mG3 are activated and gate G7 when output 251 is reached. Such frequency fluctuations are also passed on to the 90 degree phase-shifted alternating current. The control element is shown in detail in FIG. 27a.

The pulses Jn and also the start signal are connected to the gate G3. If both are present, G3 takes effect and brings the bistable member bG into the working position, which now applies working potential to the gate G1. Only now can the Jp pulse take effect. The control pulses Js now reach the counter via the gate G2, which is only a potential reversal gate. The other processes on the counter have already been described.

 In FIG. 2.7, the negative half-wave can either be generated by the Jn pulse, or the passage of the positive half-wave is repeated, the respectively marked outputs being stored.

 The code used in the invention can. preferably be an amplitude and / or phase code, e.g. such is shown in Fig. 16. With a pure amplitude code you can also use 2 alternating code currents; Provide frequency, one of which is then shifted in phase by 90 degrees during the transmission and is subsequently added to the other.

The principle of the invention can also be used for the transmission of digitized speech. FIG. 28 shows 5 alternating coding currents with a binary code, the characteristic states being a large and a small amplitude value of the respective half-wave. The frequencies are 8, 12, 16, 20 and 24 kHz.

This gives 20 bits, if two alternating currents of the same frequency are provided, but phase-shifted by 90 degrees, this gives 40 bits, ie with 8 bit code words as shown in Fig. 28a, 5 digitized voice channels can be transmitted. In FIGS. 21 and 22, 2 sound taps per line are sufficient at a tap frequency of approx. 30 kHz (PAM) per line

at the beginning of the respective image line and in the middle of the

The distance is then 32 μs.Each tap is then converted into an 8-bit code in the analog / digital converter A / D and is then, as shown in FIG. 21a, sent with the following 5 luminance code words. In Fig. 21a e.g. with 1 / 9,10,11,12 and V / 9, 10, 11, 12.

The taps during the picture change time must e.g. be determined by a time measurement. The coding then also takes place during the picture change time.

Any code, such as the AMI or HDB3 code, can of course be used for the code multiplex. In the examples, an amplitude code is often used in which the code elements from the half-waves or Periods of a sinusoidal alternating current with the characteristic states small and large amplitude value exist. One code element corresponds to one bit. If, for example, 12 bits are required for the composite signal and audio signal, 12 half-waves are required. The coding can be carried out synchronously with the taps, since the length of the code words does not change. However, if a phase code is If a phase code is additionally provided, the period duration also changes with each phase change, so that with a periodic tap and with phase changes being rectified, the signal taps are no longer in synchronism with the code. For communication there are 2 possibilities - apart from buffer storage - to restore the nominal frequency once with each phase change until the next phase change, e.g. in Fig. 4 the nominal frequency f2 is followed by a phase change T = f1 and the following codes have the same phase changes, the following will be the following Coding coded with the nominal frequency f2. Only when phase f1 changes again does a phase change take place with respect to the reference phase, ie the reference phase must be saved at the receiver. This can be transmitted by the transmitter, for example, during the blanking time. Another possibility of avoiding overlaps of two taps is that the transmitter measures each code word between the end of the code word and the previous and the following tap. Is the danger of an overlap in the leading or trailing direction, code words with the smallest or longest period are interposed. Such are shown in FIGS. 29a and 29b. This can be avoided by storing lines.

In Fig. 19 a code element has 6 different levels and 2 digits the code word, as a result. 6 to 2 combinations are possible, i.e. 36 combinations. With 32 combinations you get 5 bits. In FIG. 21b, a code element can also assume 6 levels, so that 6 = 5 for 5 digits

5184 combinations are possible, i.e. at least 12 Öit.

At 12 bit. you get 4096 combinations.

 In Fig. 22 the PAM for the sound is generated in the TSO element and in each case e.g. placed in half rows at 6c. The connections 6c and 6d are not required if the sound and the other signals are placed in the blanking time, so that the concentrator K 1 then takes over these tasks.

With the help of Figs. 21, 22 and 23 it should be shown how, for example, code multiplex can also be used for television. The transmission frequency can of course be significantly reduced if more amplitudes and / or phase stages are provided. It is also possible to combine it with different supports, as provided for example in patent application P 3229 139.6 Fig. 9, or with different current paths. For example, in Fig. 28 with 8 KHz a 64 Koit voice channel can be transmitted, with a binary code. 2 digits are each marked by the two half-waves of an 8 KHz alternating current, 2 further digits by the 2 half-waves of an alternating current, which is 90 degrees out of phase. These two alternating currents are summed and transmitted as one alternating current via the one current path. The same is done via a second current path, so that the code word has 8 digits and 2 stages, so that 256 combinations are obtained. After the evaluation of the semi-wool and of course intermediate storage, decoding is carried out on the receiving side. The coding can also be duobinary. Another method, in particular analog signals such as speech, tones, the lumianance signal in television, the color signals in television, telecontrol values, to be transmitted frequency-modulated and with less bandwidth, consists of the size of the PAM pulses in FDM with the help of pulse duration modulation PDM

Convert pulse lengths. These PDM pulses can then be in

AC pulses e.g. can be converted according to the method of FIG. The pulses are then resp. Periods of an alternating current are formed, the. Periods or Half-periods of the half-waves or Periods equal to the length of the PDM pulses.

 The spectrum of the frequency-modulated oscillation used to date contains a large number of side oscillations above and below the carrier, so that a very wide band is required for the transmission. The bandwidth required is larger than twice the frequency swing. In the circuit according to the invention, predominantly digital ones can be used

 Switching means are used so that inexpensive production is possible

 The method will now be explained in more detail with reference to drawings. First, known circuits are explained again, which are necessary for the generation, among other things (European patent application 0284019). 2 Execution examples of the invention are described below. First, the principles of the two versions are summarized. The information is modulated once in pulse amplitude and in the

 Consequences are converted into pulse durations with the help of the Aquidestanz process, or the information is immediately included

 Coded in pulse duration using the sawtooth method. This

 Pulse durations are then converted into rectangular pulses in connection with the pauses between the pulse durations and subsequently with the aid of filters to sinusoidal coding alternating currents. The pulse durations and pauses are reshaped with the help of counter elements in connection with electronic components

 Switches. The pulse duration then corresponds to the farmer

Half period or Period of the coding alternating current. If the pulse duration is small, the frequency of the half-wave is Period when the coding alternating current is high, the pulse duration is long, see above is the frequency of the half wave or Period when coding alternating current is small. On the receiving side, the evaluation is carried out, for example, by measuring the half or Periods. So there is frequency and phase modulation at the same time.

 In the second embodiment, the pulse duration pulse, in Fig. 32PD1, PD2 and the pause between the pulse durations (Fig32, -P) - the pulse duration and the pause correspond e.g. each the distance between two taps, denoted by tp in Fig. 30 - fed to an electronic relay, in which bipolar rectangular pulses are then generated. Filters are then used to generate the frequency-modulated coding alternating current.

 In FIG. 7 it is shown how with the aid of a counter Z in connection with the frequency of the indexing or Measimpulse generated in the oscillator Osc, the time of a pulse is determined. The respective output of the counter then marks the time. This is then provided in connection with gates for the control of an electronic relay ER. This then generates bipolar rectangular pulses.

 The function is as follows. In the Osziliastor Osc, the advance or Measuring pulses generated for the counter Z. These reach gate Z.1 via gate G.1 as long as the start character at B is present. In the example, only the outputs Z1 and Z2 of the counter are required. These outputs are at gates G2 and G3.

If the half-period of the pike pulse J is to have the size of the sum of the measurement pulses up to Z1, the encoder sets the g3 h potential so that when output Z1 is reached, a potential change takes place at the output of G3, which causes the electronic relay ER to trigger the rectangular pulse to end. If this was a positive impulse, the next impulse becomes negative. The counter is then switched back in this position. For this purpose, gate G4 is provided at output z2. From the encoder, the oscillator frequency can also be increased or decreased via fA, so that different times could be marked with the respective outputs, for example. A connection A also goes from the encoder Cod to ER, with which one can control different pulse sizes J. The square-wave pulses are applied to the line as a sinusoidal coding alternating current via a low-pass filter TP, the transformer U and filter Fi. The half- Period of the encoding alternating current is the same as that of the rectangular pulse.

The principle of converting the square-wave pulses into a sinusoidal alternating current is shown in FIG. E.g. Rectangular pulses with the frequency 1 MHz with a low pass 5.5 MHz band-limited, so you get, as shown in Fig.3c, still fairly steep edges. In Fig.3b, a low pass of 3.5 MHz was used: you can see that the slope has already decreased noticeably.

In Fig3 a a low pass of 1.5 MHz is switched on, the receiver has a sinusoidal alternating current. The periods are the same as those of the rectangular pulses, i.e. one can, respectively, the period durations as a measure of the frequencies. Take phases. In Fig. 7, this principle was used when converting the rectangular pulses J into an encoding alternating current with the help of the low-pass filter TP.

Fig. 4 shows rectangular pulses of different periods, expressed by the frequencies f, f1 and f2. These rectangular pulses have different phase shifts relative to one another, different frequencies. It can be seen from this that by changing the periods, phase jumps or Can cause frequency jumps, so that you also get a frequency modulation. Such a phase or Frequency step by step. This ensures that the bandwidth becomes small. As can be seen from FIG. 6, a total phase shift of 40 degrees is obtained with phase jumps of 5 degrees each 180 degrees with 4 phase jump steps.

 FIG. 30 shows PAM-coded pulses from a signal Inf. These are converted into pulse duration pulses using an equidistance method, as shown in FIG. 30b. The distance between the PAM pulses (Pig30atP) corresponds to a pulse duration PD and a pause P, as in FIG

Fig30b shown. Pulse duration modulation can also be saw tooth process. In the Fig. 31 and 32 this procedure is shown. The pulse durations are rectangular pulses PD1, PD2 .... Furthermore, the symmetrical PDM and the bipolar PDM are known. (see also book

 "Modulation method" by Stadler 1983).

In the Fig. 35 shows an embodiment according to the invention. In the pulse duration modulator PDM, the pulses are generated, for example, according to Fig. 30 or 32, and fed to the gate Gl via G5. The measuring pulses Jm, for example 100 kHz frequency, are located at the other input of the gate Gl. As long as there is a PD pulse at Gl, the measuring pulses Jm are effective at the output. Via the potential reversal gate G2, the measuring pulses reach the counter Z, which is controlled with these pulses. The number of outputs on the counter corresponds, for example, to the distance between 2 PAM pulses, in Fig. 30a tp. The tap frequency is 10 KHz, then the counter would have 100,000 outputs. The frequency swing is determined by the largest and smallest amplitude value of the information Inf, denoted by gw and kw in FIG. 30a. The outputs A of the counter Z lead to gates G3 and the outputs of the gates to gates G4. The respective PD pulse that blocks gate G4 is located at the other input of gate G4 (only when the PD pulse is no longer present can the output potential also become effective via G3 at G4. ER now receives a potential change indicator via G4 for the next rectangular pulse, the beginning of the rectangular pulse is marked by the respective PD pulse, the next rectangular pulse is determined by the pause P (Fig. 30b, P). From ER a potential is applied to gate 5 via P, and thus to the gate Gl the measuring pulses Jm become transparent again. The counter z is now switched to the output of gate G6. When the next PD pulse comes back, G6 becomes effective and the counter is switched back to the starting position via R. Rectangular pulses RJ are then at the output of ER the size of the half-periods such as that of the PD pulses and the pauses P. In the filter Fi, the rectangular pulses become (sinusoidal half-waves fmo, so the information is frequency-modulated. The half perio of the useful signal modulation frequencies then move between the half-periods on the counter with kw and gw marked. In Fig. 33, for example, kw = 15 KHz Center frequency 10 KHz and in Fig. 34 gw = 7.5 KHz. in the

For example, the pulse dansers can change by half.

this is a matter of dimensioning the pulse width modulation circuits. The half-waves of the breaks have in Fig.

 33 a lowest frequency of 7.5 kHz and in Fig. 34 a highest frequency of 15 kHz. The half-wave amplitudes always remain the same. The evaluation on the receiving side is carried out by measuring the half-periods. Synchronization is not necessary because the zero crossings of a period when encoded using a

 2AM code the taps at the same time, so only the positive half-waves have to be converted into PAM pulses.

The PAM pulses are then one period behind on the receiving side.

The redundancy of the pauses in Fig. 35 can be avoided if, for example, the PAM pulses are saved and the next EAM pulse is called up after each PD coding. However, synchronization is then required at the receiver. When using the PAM on the transmission side, the tap frequency would have to be synchronized from time to time. 36 shows the basic circuit of such a circuit on the transmission side. The PAM pulses are stored in the memory Sp. The ER receives the next pulse via AR. In preparation, the next pulse was saved as a PDM pulse in memory Sp1. The counter Z is now controlled via the control element St and set to a corresponding output. ER also brought the counter back to the starting position via R. The control impulses Jm are also on the control unit. When the PDM pulse is called up, a PAM pulse is also sent from the memory Sp to the duration modulator and stored in it as a PDM pulse until the Sp1 memory is free again. It is advisable to provide 2 Sp1 memories, which are then alternately connected to the control unit after each call of ER. At the end of the PDM pulse, a pulse end criterion is given to ER via counter Z, G1, G2. The square-wave pulse PD generated by ER is reversed to the next, the counter is switched back via R and the call of the next most PDM pulse ice initiated. The rectangular pulses RJ are passed on via a filter. Half waves with the half-period durations of the PDM pulses then arise at the output of the filter, as are shown in FIG. 37. In Fig. 38, the PD pulses and possibly pauses of Figs. 30b and 32 directly control the electronic relay ER. A polarity reversal occurs after each square-wave pulse. With the uninterrupted sequence of PD pulses achieved by storage, as shown in Fig. 36, the ER relay can also be controlled in Fig. 38. A polarity reversal is only required after each pulse. In Fig. 38, the beginnings of the PD pulses are only marked via PDS if a continuous transmission of PD pulses is to take place. In the case of a pulse / pause transmission, the start and end of a pulse are marked anyway.

 If you want to be free of direct current during transmission, the respective pulse must be coded equally by a positive and negative half-wave. This can e.g.

 by storage in a shift register, in which case a wired halving of the respective overflowing outputs or a halving takes place during the evaluation by means of a computer. A division into 2 half pulses can also be achieved using the symmetrical PDM.

The PDM pulses of FIGS. 32 and 32a can also be connected directly to a filter Fi according to FIG. 38. In order not to allow the bandwidth to be increased, it is then expedient, as shown in FIG Place information in the sawtooth voltages so that the difference in length or The width of the pulses does not become too large. The PD pulses according to Fig. 30b can also be applied directly to the ER switching means. After each pulse, a polarity reversal or no potential must then be applied to the rectangular pulses. The rectangular pulses would then be unipolar. In order to also reduce the bandwidth in the case of the equidistance method with direct control of the ER switching means, a larger direct current bias (in the case of unipolar PAM) or a corresponding dimensioning of the circuit for the generation of the PDM would have to be carried out when the PAM pulses were generated. 39 shows 4 channels with a half-wave coding with the characteristic states of large and small amplitude values. The frequency is the same for all 4 channels.

These 4 channels are used to encode the color television signals. 8 bits are for the Y signal (luminance signal), 4 bits each for channel a and b. 2 bits each in channels a and b are intended for ion and other signals T + S. Channel c is available for coding the red signal and channel d for coding the blue signal, each with 6 bits. In each case 2 channels are then, according to FIG. 11, vector I, (k1, k2) with the codes I, (II), IV,

 (III) summarized so that a total alternating current is generated according to Fig.9. The phase position of the two total alternating currents is then set to 0 degrees and 90 degrees. These two total alternating currents can now be transmitted on the basis of quadrature amplitude modulation, so that a narrow band is required for the transmission of all color distorted signals and other signals. Transmitted as double QAM, i.e. Channel a + b are modulated in quadrature amplitude and channels c + d are modulated in quadrature amplitude, whereby the channels have a phase angle of 0 °, 90 °, 90 ° and 180 ° and their total alternating currents have a phase angle of 45 ° and 135 °, and that the two total alternating currents again modulate quadrature amplitudes the evaluation is more difficult, as can also be seen from FIG. 11 (vectors 1, 11 and III arise with a single QAM).

You can or the 4 channels. their binary values are also transmitted in a code-multiplexed manner. Fig. 40 shows the binary values of the 4 channels again. According to Fig. 41, 2 rows of Fig. 40 are to be combined into 8 bits. In Fig. 39, 6 MHz is the frequency of the alternating currents; 18 MHz is then required for the coding. If FIG. 41 uses a duobinary coding corresponding to FIG. 62 with the half-waves as code learning distance, one would gain some bandwidth compared to FIG. 39, but the frequency would be 3 times as high. If you combine the rows 1, 2, 3 and 4, 5, 6, i.e. 12 bits together for this duobinary code, a 3-step code word with 8 digits is required for a row 1, 2, 3. 8 digits mean 4 periods, so a frequency of 2x24 MHz would be required, al-. too high for this purpose too. Fig. 45 shows a 4-level code element, with 4 digits this gives 256 possibilities. Coding according to Fig. 41 would result in a frequency reduction to 36 MHz. 63 shows a 6-stage code element. In order to code 3 rows of Fig. 40 serially, i.e. 12 bits, 5 digits would be required. So 30 MHz would still be required. In addition to the 3 amplitude levels, there are two phase levels. Periods provided. Fig. 46 shows 3 amplitudes and 3 phase steps. If 2 rows with 12 bits each are formed on the arrangement of Fig. 40, 3 digits are required for each row, 6 digits for both rows, ie it is one Frequency of 13 MHz necessary.

In Fig. 43, the color television signals are arranged in a different way. 8 bits for a Y tap (Duminance, pixel B) are 4-bit serial, the colors red or blue 3-bit serial in the row III + IV. The 4th bit in rows 3 and 4 is intended for sound and other purposes. The color red or blue comes with every 2nd Y signal, i.e. these are constantly changing. If the vertical rows 1/2 and 3/4, as shown in Fig. 44, are combined, coding results in a more favorable ratio. With 4 stages, 3 digits are required, a frequency of 18 MHz is then required. If rows 1/2 and 3/4 are arranged in parallel, i.e. 16 bits, 4 digits are required for coding according to Fig. 46, i.e. 12 MHz frequency.

The double QAM of FIG. 39 can be transmitted frequency-modulated in order to have even more security during the transmission. The total alternating current has only small frequency changes, so that, as can be seen from Fig. 64, the frequency-modulated oscillation can be transmitted in a narrow band. It can be seen from this figure that the half-period T / 2 becomes very small when the frequency is increased, that is to say the frequency increases sharply. With a modulation frequency Mf and an amplitude u, the half-period T / 2 is shorter, with double amplitude 2u the half-period is shorter, while with an additional double frequency M2f, the half-period is significantly reduced.

Fig. 47 shows an overview of a television transmitter in which the codes explained in FIGS. 40, 41, 43 and 44 are used. The analog tapped signals come from the multiplexer (not shown) into the

Analog-rich ASp and from there 'the samples are passed on to one or more analog / digital converters.

The digitized signals are then stored in the digital memory DSp and subsequently fed to the folder. In this they become according to Fig. 40, 41, 43 or 44

orderly. In this order, they are fed to the encoder.

According to the predetermined code e.g. according to Fig. 45 or

46 or 62 or 65 encoded and fed to the modulator MO - the oscillating current is sent to the modulator by the oscillator

supplied and the modulated transmission alternating current via amplifier stages (not shown) and the final amplifier

Given antenna. An overview of the receiver for evaluating the coded signals is shown in FIG. 48. The SebdeewechseIstrom comes via the receiving antenna E in the stages tuning circuit / amplifier, mixer / Oszillaotr Mi / Osc, via the intermediate frequency amplifier. IF to the demodulation stage - the input is connected like an overlay receiver for radio reception - the code change current is available at the output of the demodulator. This is switched into the decoder. The signals tapped in the transmission multiplexer are received here again, like the Y, r-y, b-y. Sound and other signals S and the various circuits supplied.

 50 and 51 show analog encodings of the color television signals. An alternating current of the same frequency is provided as a code alternating current in FIG. The half-wave amplitudes are the code elements. The tap sequence is y, r, y, bl, y, T + S etc. The transmission of these analog coded signals takes place on the basis of frequency modulation, so that a narrow band - only one frequency Fig. 64 - and also a transmission security is obtained.

An analog code is also provided in Fig. 51. It is a phase encoding. The analog code is given by different half-period lengths. The amplitudes of the half-waves are always the same size, it is a kind of frequency and phase modulation. The individual signals are aries arranged in series, in the example y, r, y, bl, y, T + S. The transmission takes place at a tap frequency of the Y_ signal at 6 MHz at 6 MHz. If all signals are multiplexed, including the r, bl and T + S. Signals, a tap frequency of 12 MHz is required.

In Fig. 52 there is a coding corresponding to Fig. 51

provided only the sound and other signals T + S

are encoded by a superimposed amplitude code.

It is a binary code with a large and a small amplitude. The values of the Y and the r + bl signals are given by the

Half-periods set. In synchronism with the PDM pulse, e.g. the respective amplitude value is given to the ER relay of FIG. 36 in which a square-wave pulse with low or high voltage is then generated. The amplitude code elements can e.g. multiple channels, v / ie sound stereo, etc. In Fig. 55, the 4 half-wave elements are assigned to 4 different channels.

An evaluation of the PDM, PPM or PFM pulses encoded with the half-periods is shown in FIG. 59. This is done again with the help of sawtooth tension. At the beginning of a flat wave, i.e. at the .lull passage, the generator of the sawtooth voltage is switched on, after the half wave at the next zero crossing, the sawtooth voltage is briefly connected to a capacitor, for example by means of a field effect transistor, and stored in the capacitor. The half-period T / 2 is then equal to the voltage value T / 2 or, analogously, the magnitude of the voltage value. The half-period of 1 corresponds to the voltage value u1, that of 2 corresponds to that of u2, etc. If pulse amplitude modulation was carried out on the transmitting side of speech at 8 KHz, the voltage u1, u2, u3 must be tapped on the receiving side at the same frequency and converted to the voice alternating current . In the case of a time-multiplexed tap of several channels, the stored values u1, u2, u3, ... must be redistributed with the same frequency of the time-multiplexed tap. The original information can be produced, for example, in the way by forming the evaluated code u1, u2, .. after the channel allocation in a step-like manner and passing this step signal over a low pass. Such reform are known and are therefore not dealt with in more detail.

 PPM pulses can also be decoded in the same way as in FIG. 59 the PDM pulses. This is shown in FIG. 60. The distance T / 2 of the pulses is converted into PAM pulses again using the sawtooth method and stored. The distance T / 2 then corresponds to the voltage u1 etc.

When transmitting television signals according to the principle of

Eig.36 and 38, the evaluated signals must be distributed synchronously on the reception side. In the Austas.tzeit synchrαnisierirapulse must be sent so that the sampling frequency on the receiving side, the distribution frequency can be determined according to the transmission side. The sum of the largest half-periods per line that may occur must not exceed 54 us, this is the time that is provided for a line with a 4: 3 aspect ratio. As a result, the half-periods in the transmitter may also have to be measured. there must also be a fill code in the line code, which contains, for example, the smallest or largest periods in a specific sequence. Of course, other fill codes can also be provided. In addition, the blanking time must also be provided as a fill code. In Fig. 61 the smallest and largest half-periods k and g are shown. Such can e.g. are sent alternately.

 On this basis, several channels can also be combined via one transmission path. Such an example is shown in Eig.56. The multiplexer Mu combines the channels 1 to n in terms of pulse amplitude, which is well known. These PAM samples are stored in the memory Sp, called up by the PDM and, as already described, fed to the counter via a control unit St, to which the control pulses Jm are connected. The other switching operations are the same as e.g. described in Fig. 36. After the pulse detector modulator PDM, the pulses can also be processed directly in accordance with FIG. 38. On the receiving side, of course, synchronization and distribution must take place in accordance with the tap frequency of the multiplexer.

Another possibility of multiple use of a current path is shown in FIG. To the Codiet alternating currents To be able to separate in terms of frequency, control pulses are used such that the frequency ranges of the alternating code currents are at such a distance that a correct evaluation is possible, for example by means of a filter in the receiving station. In Fig. 57 Z1 is the one converter with the control pulses Jm1 and Z2 the other converter. Counter with the control pulses Jm2. In the

Fig. 58 shows the frequency position of the two channels.

 T / 21 and T / 2II are the lowest frequencies of the two channels. The respective angular stroke f2 brings the frequency range of channel T / 21 closer. I el is still a distance from Ab. This can be chosen so that inexpensive udders can be used.

Below are some codes with which you can encode and transmit data with a frequency, in the example television signals. 53 shows a binary code in which the amplitudes of

Half waves with the characteristic states of large and small amplitude values are provided. A bit can then be encoded with a half wave. There are 8 bits for the Y signal, 6 bits for the red and blue signals, and 2 bits for the sound (digitized) and other signals. Red and blue alternate, such as shown in Fig. 51, coded.

With 6 meg taps for the Y signal, an encoding alternating current of 48 MHz would be required here. A duobinary coding is provided for this in FIG. The coding alternating current then has a frequency of 27 MHz. You can transmit these coding alternating currents again frequency-modulated, the frequency band does not become too wide, as shown in FIG. 64 emerges. The transmission security becomes even greater. A possibility is recorded in FIG. 66 of how a message can be transmitted digitally in narrowband fashion without modulators. Each code element is assigned a plurality of periods of an alternating current of a frequency, which are determined by the time Og, that is to say a predetermined number of periods. The coding is assumed to be binary. With each change of state, i.e. 1 to 0 or 0 to 1, the transition takes place continuously, marked with Ü in Fig. 66. The amplitudes for zero have the large Ak and for the characteristic state 1 the Great Ag. If the same values come in succession, the amplitude size is not changed. With 5 identical values one would send a period number of Og with the same amplitude five times. The transition to another characteristic state is calculated, for example, to the following characteristic state, for example Ü + O = Og.

The coding of information according to FIGS. 53, 54 and 66 results in very narrow frequency bands. This can also be used in television technology. So you could possibly put more channels between the individual television channels. An example of this is shown in FIGS. 42 and 82. The carrier BTz is provided for this in FIG. The carrier is also taken along for modulation. It is thus coded according to, for example, FIG. 66. As can be seen from FIG. 42, the carrier is also respectively in the image channel gap. the carriers are provided for the sound information. With VHF it is necessary, for example, to provide a series resonance circuit for the next higher television channel. Suction curve. The resonance resistance is only as large as the terlust resistance. The Nyquist flank is hardly affected. When the FBAS signal is modulated at 38.9 MHz, a suction circuit Er is arranged after the residual sideband filter, as can be seen in FIG. Such a series resonance circuit is easy to implement. A basic circuit diagram of the accommodation of an information channel between two television channels is shown in FIG. The image signal B (luminance signal), the modulated. Color carrier oscillationF and the blanking and synchronizing signals AS are added to the PBAS signal in the adding stage. The CVBS signal is then fed to a modulator Mo with the carrier frequency of 38.9 MHz via an amplifier stage. The amplitude-modulated signal is then fed to the residual sideband filter, so that the lower sideband is partially suppressed, as is known. After the RFi, the series resonant circuit is arranged in the circuit. The resonance frequency here is 37.9 MHz. The resonance curve is designated RR in FIG. 42. At 6 MHz above the image carrier in the example, the additional channel receives a carrier or Coding frequency of 189.25 + 6 = 195.25 MHz. This is the frequency of the coding according to Fig. 66. In the example, several channels are combined time-multiplexed on a PAM basis (K1-X) and fed to the encoder. In this there is also a PAM / PCM converter, which converts the serial incoming PAM pulses of channels K1-X into a binary, duobinary or other code. An oscillator feeds the encoder with the carrier frequency of 195.25 MHz. This alternating current is then modulated with the PCM pulses analogously to a code from FIG. 66. The modulated carrier is then fed to a decoupler E, to which the modulated sound carrier is also connected. Both signals are then possibly via an amplifier of a crossover W, to which the carrier of the composite signal is connected, in the example 189.25 MHz. The sound carrier has a frequency of 194.75 MHz. All carriers are thus guided to the common antenna via the switch. The series resonance circuit for the additional channel of 195.25 MHz is thus arranged in the television channel with the transmission frequency of 196.25 MHz. These additional channels can be evaluated, for example, in accordance with that of the audio channels.

If the transmission frequencies are very high, a television channel can also be accommodated in the additional channel.

The digital code of Fig. 66 can also be modified as an analog / digital code. There is an amplitude change for each value. The PCM technique is used for illustration. With this technique, 256 quantization levels are provided, for example. For the largest PAM value, one could foresee 256 periods. At half the size, 128 periods would be necessary. If this were the following value, these periods, which are always of the same size, would be used to distinguish the coding from the beginning. Accept a different amplitude value at the end of a value. In practice, this would of course be changed, for example assigning 400 periods to the largest value. The value 1 would then have 1 43 periods, half the size would then have a period number of 143 + 128 = 271. Depending on the frequencies available, even higher period numbers can be used. 68 and 69 show a method for coding the color beard signals red and blue. In this, the color characteristic values are tapped at a predetermined frequency and modulated on each carrier, which are 90 degrees out of phase with respect to one another. The carriers have at least twice the tap frequency. These are summed up. The total alternating current contains the position of the color vector in the color circle due to the phase shift compared to a comparison alternating current. This bubble shift is caused by the period. Residual period compared to the comparison alternating current. Storage of these values is necessary for a double carrier frequency up to half the number of taps in a line, and for three times the carrier frequency 1/3 of the taps in a line. The values of the phase shift are transferred to the half or Period duration of an alternating current included. With cable transmission one can maintain the

 Provide a period of no DC current, in which the positive and negative half-waves have the same values. In the example, the carriers have 3 times the tap frequency.

68a shows the sampling pulses P1, P2, P3, .. of the color difference signal BY. These are drawn in step-like dashed lines - expanded. A step-like expansion is brought about by a capacitor storage with a certain time constant. 68b shows the taps P1,2,3, .. of the color difference signal RY with the step-like extension. 68c and d show the two carrier alternating currents with the modulated staircase-shaped signals. The two modulated carriers are now added. A total alternating current is then obtained as shown in FIG. 68e. The amplitude corresponds to the size of the color vector, this is a measure of the saturation of the color and the phase shift in relation to a comparison phase then corresponds to the color tone in the color wheel. This is already the case with the NTSC systems and PaL are known and will therefore not be discussed in more detail. The output resp. Comparison phase V _g is in the

Fig. 68f shown. The phase shift therefore always remains in the example during the 3 periods of the carrier Su. Immediately in the event of a phase change, the half-period cannot be measured, which is why at least 3 periods are provided in the example until the next phase change. As can be seen from FIG. 68g, a coding half-period is composed of 2 constant periods KP and the actual coding phase shift Ph, which is almost a period at 359 degrees phase shift. The individual processes of transferring the phase shift to the period are shown in FIG. 69. For this, 3 color circles are shown with the phase shifts 60, 120 and 240 °. The start of measurement is designated in the Mg, 68g and in Fig. 69 a, b, c with Eh0 °. In the example, the burst would have a phase angle of 0 ° as shown in dear Fig. 69d. A 3urst is not necessary in the example because the transmission is determined by the absolute period value. It is advisable to code the beginning of the serial arrangement of the code elements for each line. The half-period, i.e. the pulse that controls the ER relay in Fig. 75, begins with Be in Fig. 68 f and lasts for the two periods and also the size of the phase shift Ph. In Fig. 69a, the phase shift is 60 ° a phase shift of 300 ° was measured. The total pulse is then equal to the two periods + the length of 300 °. This pulse is amplified, for example, by ER relays and then converted to a sinusoidal coding alternating current using a filter, as has already been described many times. The length of the half-periods in a television line thus becomes smaller than the distances between the sum of the step signals and the color difference signals. Therefore, the sum of the half-periods must also be measured and, if necessary, a filling half-period must be inserted if one is appropriate

assigns the duration of 3 periods of the comparison alternating current. The alternating currents shown in FIGS. 69a, b, c me are total alternating currents Su. In Fig. 69b the color angle is 120 °, the measurement is 240 ° and in Fig. 69c the color angle is 240 °, the measurement is 120 °. The measured period is added to the two constant periods KP. In the examples, the saturations are 100% respectively.

70%. As with the PAL system, these go into the amplitudes. 69d shows the phase comparison alternating current. The period of a period of the total alternating current b maintain the phase angle of 360 degrees. To get even more accuracy, you can provide 180 degrees for a period by making an additional mark. If the phase shift is up to 180 degrees, a phase shift over 180 degrees is measured, as can be seen from FIGS. 69a and b. Here it is only necessary to measure the phase shift of the positive half period. Since only the period is required for coding the pixel size in the half-periods, an amplitude code can be used to code that the angle is more than 180 °. When transferring, you can then transfer twice the value of the angle. In Fig. 69a the angular size dw can then become twice as large. The amplitude code must then be evaluated in the receiving station and the additional 180 ° angle taken into account. The color and pixel coding can be transmitted in parallel in a manner similar to that disclosed in FIG. 58 or in series as shown in FIGS. 70 and 71. In the examples, the pixel tap is twice as fast as that of the color signals. Since the code alternating current is to take place in an uninterrupted sequence of positive and negative half-periods, there is no synchronism between tapping and coding. A more or less large storage is therefore necessary on both the transmitting and the receiving side. At the receiver, the pixel and color signal assignment must be made exactly at the tap frequency of the transmission side. The color vector size, in Fig.

69a, designated VS, is coded by the amplitude size, which is stored like the period. A possible arrangement for the transmission is shown in Fig. 70. The required frequency is determined by the number of image taps and color type tap number determined. If 832 pixels are to be tapped in a line and (a half period is required for each pixel, then 416 periods are required for the pixels. For the color coding, 1 half period must be provided for every 2 pixels, that is, 213 periods for a line. For example, these 629 periods are assigned one Time of 52μs available. The frequency and the smallest frequency of the coding alternating current is then predetermined. The blanking interval of 12 μs is given the same frequency. Since the coding half-periods are always smaller than the calculated ones, filling half-periods must be provided which are expedient for the greatest period A different code can of course also be provided for these. The pixel half-periods always have the same amplitude size, while for the color half-periods the color vector is coded with the amplitude magnitude, that is to say the saturation is coded Pixel half-period n are provided, can be provided as coding for the filling half-periods. The storage of the amplitude size of the color or Saturation vectors can take place by means of a capacitor which is connected to the coding alternating current Su via a diode. The pixel half-periods B (Y) can also be overlaid with a binary or duobinary amplitude code, with which the speech and other signals are then digitally encoded, as already described in FIGS. 52, 55. In Fig. 71, a pixel coding is also assigned a binary coding for a phase angle of the hue greater than 180 °. In Fig. 69a, for example, it is found that the counting half-period dw is positive, so that the negative half-wave no longer needs to be measured. These 180 ° are determined by this coding B + 180 °. The value dw becomes twice as large during transmission, so that the accuracy increases. The further pixel half-period B + T / S is overlaid with a binary or duobinary amplitude code, with which the digitized speech and other control signals are then encoded. The half-period F includes the hue angle in the half-period duration and the color or analog in the amplitude size. Saturation vector. 72 shows the principle of an interconnection of the

Half periods are shown with the amplitude code. An electronic relay again supplies square-wave pulses RJ. The period of these rectangular pulses is marked with Ph. In the folder Or, memories are provided in which the pixel taps may already have been stored in half-periods. In addition, a memory is provided for storing the color angle KP + Ph. The amplitudes of the rectangular pulses are supplied to the electronic relay ER in the folder Or in synchronism with the half-periods. The analog amplitude size of the color vector is retrieved from the memory via FA. Via T + S, the digitized sound and other signal amplitudes are called up from a memory and sent to the electronic relay in the order e.g. of Fig. 70 fed. Such an electronic relay with several amplitude stages is shown in FIG. The square-wave pulses with the corresponding period durations and amplitude stages are then at the output of ER. These are then converted into a sinusoidal alternating current in the filter Fi.

The direct measurement of the phase angle is also possible. The zero crossings from BE Fig. 68g must then be counted with the sum current, so that e.g. can determine the zero crossing M in Fig. 69b. From this point, the measurement is carried out up to Ph0 °. Ph in Fig. 68g could then e.g. spread over 90 ° of the phase shift. The 3 remaining 90 degree angles would then have to be coded with 180 °, similarly to FIG. 71.

The coding alternating currents of FIGS. 70, 71 are modulated onto the transmitting alternating current and transmitted. The receiver is then switched in principle as shown in Fig. 23. The input signals are routed via the tuning circuit / amplifier HF mixer / oscillator via the intermediate frequency amplifier V to the demodulator DM. The demodulated alternating coding current, for example according to FIG. 70, is fed to the decoder DC. In the case of a serial arrangement of the coding half-periods, the distribution of the image and color values (FIG. 70, 71) must take place in accordance with the image point and color difference signal taps. It is therefore expedient to send an alternating current at the sampling frequency during the blanking time, which is then used for the synchronization of the im Receiver provided as a distributor synchronized alternating current. The amplitudes of this synchronizing alternating current of the blanking time can also be provided for binary or duobinary coding. The pixel values can be evaluated, for example, according to Fig. 59. The evaluation of the color mode element with the half-period values and the amplitude quantities, which if necessary is converted into a length similar to that shown in Fig. 74a, is best carried out on a computational basis. The sound (stereo) and other signals that are PCM-coded can be demodulated in a known manner.

 Fig. 67a shows the pixel taps BAb and the color difference signal taps FAb and, in addition, how to use them e.g. with serial transmission (Fig. 70) the coding alternating current can be assigned (Cod).

 Fig. 79 shows a particularly useful coding method.

 The coding method according to Fig. 79 works with binary

 Code elements that take the form of a period or a

 half period of a sine wave and in which the binary values 0 and 1 by a small or large amplitude of the period or half period of the sine wave

 are shown, as is known from the above-mentioned US Pat. No. 4,675,721. In Fig. 79 it is assumed that the code elements consist of alternating positive and negative half-periods of a sine wave, with a relatively small amplitude of the half-period

 Binary value 0 and a relatively large one (e.g. twice that

 large) amplitude of the half period represents the binary value 1.

The code shown in Fig. 79 allows the representation of a nine-digit binary number. It is as follows

 built up: The bits of the first and second digits

of the nine-digit binary number to be encoded are indicated by

the first, positive half-wave 1 and the subsequent one

second, negative half-wave 2 of a sine wave

Period P shown as in curve a in

Fig. 79 is shown. The bits of the third, fourth and fifth digits of the

The nine-digit binary number to be coded are generated by the successive half-waves of a sine wave

the period 2P / 3 shown as the curve b in

Fig. 79 shows. The sixth, seventh, eighth and ninth bits of the nine-digit binary number are represented by the successive half-waves of a sine wave of the period P / 2, as curve c in FIG. 79 shows. The

Sinusoids in curves A, B and C are all shown in the first period P1 to simplify the illustration with the same amplitude that encoded

Binary number would consist of nine ones.

In the following periods P2, P3, ... the

following nine-digit binary numbers encoded in the appropriate manner. The curve 00 shows the value 00 in the period P2 and the value 10 in the period P3.

The oscillation trains corresponding to curves a, b and c that are created during coding are superimposed on one another and can then be transmitted over a single line. On the receiving side, the vibrations a, b, c are separated by filters and can then be decoded in a known manner, e.g. B. by measuring the duration of each half period, as described in US Patent 4,794,621.

 The coding method described with reference to Fig. 79 can be modified in many different ways. For the

 Gradation of the period lengths of the oscillations for coding the successive bits, it is only necessary that within the period P, which is reserved for coding a character, there is space for a whole number of code elements (full or half sine oscillation periods).

 At the beginning and at the end of each coding period P, the different coding oscillations a, b, c etc. must always have the same phase position. You can also work with duobinary amplitude levels, so that 3

 Combinations. With an additional 90 °

phase-shifted, superimposed coding alternating current of this type are then 3 ¹⁸ combinations available. A duobinary coding is e.g. B. used in the European D-MAC system.

 The coding capacity of the method according to Fig. 79 leaves

 can be further increased by giving each coding oscillation a, b, c etc. a second phase-shifted by 90 degrees

 Assigns the coding oscillation to the same period,

 as is shown, for example, in curve a 'in FIG. 79 with respect to curve a. The two vibrations,

 so z. B. a, a ', the same period but in quadrature phase are then superimposed, resulting in a resulting vibration a ", which has the same period as the superimposed individual vibrations and therefore separated on the receiving side by a filter and by synchronous modulation back into the

 Component vibrations can be disassembled. Applying this measure to that described with reference to Fig. 79

 In this way, eighteen binary characters can be transmitted in a coding period P.

 Fig.7.7 is a circuit arrangement according to the invention

 for coding a color television signal which contains a luminance signal L, color signals I and Q, synchronization signals, if necessary, additional signals S and sound signals T. The luminance signal is tapped at a predetermined frequency and fed to an analog / digital converter A / D, which

5 converts the samples into 8-bit code characters. The code elements (bits) of the code characters become a memory

 Sp fed. The color signals I and Q are tapped simultaneously with a frequency that is equal to half

 the tapping frequency of the luminance signal, and in

 an intermediate storage ZSp cached. The buffered signals are alternately switched via a switch U4. to an analog-to-digital converter A / D, which converts the samples into 6-bit code characters. The

 Code characters are then supplied to the memory Sp.

 The synchronization signals and possibly other signals S

as well as the audio signals T, which are stereo signals,

different languages etc. can act alternately or simultaneously with predetermined ones Tapped frequency, buffered in a buffer ZSp and fed via a switch U5 to an analog-to-digital converter A / D, the z. B. 8 or 16-bit code characters generated, which are also in the memory SP. be fed. An encoder Cod is coupled to the memory Sp, of which the eight at a time, that is to say in parallel

Code elements (bits) of the luminance signal, further three

Code elements of the I or Q signal can be called up via changeover switches U1 to U3 and a code element of the S or T signal, as shown in FIG. shown in column I.

is. The short or long lines mean here

Bits of the values 0 and 1, respectively. These twelve bits are converted by the encoder Cod into a common code character, for example as described with reference to FIGS. 19 and 79.

A conventional radio frequency transmitter M is then modulated with the successive code characters, see columns I to IV etc. in FIG. 78, and the modulated radio frequency oscillation is emitted via an antenna S. The high frequency oscillation is on the receiving side

 received by an antenna E, processed and demodulated in a known receiving part ET in a known manner and the demodulated code oscillation is fed to a decoder DE-COD, as was explained with reference to FIG.

 The code words are demodulated in the decoder Dcod.

 The eight bits of the respective samples of the luminance signal L are then simultaneously available on a group 1/8 of eight output connections; in a group

 9/11 with three outputs the color signal bits that are in one

 Buffer Sp1 are buffered and at an output 12 the S / T bits, which are in a memory

 Sp2 can be cached. The luminance signal bits are converted into an analog luminance signal L in a digital / analog converter D / A. In the buffer Sp1

 the color signal bits are buffered and if six bits of an I and a Q signal sample are available, the now complete color signal code characters are converted by a digital-to-analog converter

D / A converted into analog color signals that are transmitted via a Analog memory Sp3 a corresponding output I or

 Q is supplied.

 The S / T bits are stored in the buffer memory Sp2 and, if complete code characters are available, in a digital-to-analog converter D / A into corresponding ones

 Analog signals are implemented which, if required, can be buffered again in an intermediate memory Sp4 or processed directly. During the blanking period, the transmitter M can switch others via a switch U6

 Code signals X are supplied, which are available on the receiving side at an output AT of the decoder DCod and are fed to a corresponding utilization

can be.

Fig. 83 shows a simple 4 PSK phase shift keying. The nominal frequency is f corresponding to a nominal period of 360 °. The coding is carried out by phase changes from + 45 ° to a phase of 405 ° = f1, from + 135 ° to a phase from 495 ° = f2, from -45 ° to a phase from 315 ° = f3 and a phase change from -135 ° on a? Phase of 225 = f4. The generation is carried out analogously to the arrangements of FIGS. 7 and 8. This arrangement replaces the coding previously used according to Fig.2. Such phase jumps are generally described in FIG.

 Various period durations are shown in FIG. 80. If the evaluation is carried out by dimension, it is expedient to determine clearly measurable period duration differences, as has happened at 0 °, a °, b ° and 90 °. The distances between 1, b, a and 2 should also be pretty much the same. In Fig. 81 there are phase differences of over 90 °. intended. One disadvantage is that the frequency changes become very large. In the case of cable transmission, it is advisable to ensure that there is no DC current, and the coding is carried out with the same positive and negative half-wave.

A particularly advantageous coding for code-multiplexed information transmission is shown in FIG. 19b. Half-waves of an alternating current are provided as code elements, in an uninterrupted sequence of positive and negative half waves. An amplitude code with 3 characteristic states, i.e. a duobinary code, is provided. A period then has 2 digits. In order to increase the number of digits, a second coding alternating current of the same frequency, but which is 90 ° out of phase, is provided. You get 4 digits from each period. From the two coding alternating currents, 3 to 4 combinations are obtained from each period, these are 81 combinations. In the figure, the half-wave aP1 has the characteristic state 1, the half-waves aP2 = 1, aP3 = 2,. , , the half-waves aP1 1 = 0, aP12 = 0, aP13 = 1,. , For the transmission, both coding alternating currents will be added and transmitted as only one total alternating current.

Claims

Claims:

 1. A method for coding information, characterized in that the digital and / or analog coding and the transmission of information one, two or one

 Large number of channels with less bandwidth than the single channel. the sum of the bandwidths of 2 or a plurality of channels makes up in such a way that the synchronously or quasi-synchronously arranged code elements of the channels to be transmitted are arranged in parallel (FIG. 20) and thus combined together to form a code word and / or that they are combined encoding digital or analog information, if necessary with the interposition of intermediate stages (for example, PAM), can be converted into PDM pulses, so that means are also provided which translate the values of the PDM pulses into the half-periods. Wander around the period of half-worlds or periods of a sinusoidal or sinusoidal alternating current (Fig. 35, ER, Fig. 36, ER, Fig. 38 ER)

 2. Procedure for transmitting digital signals

 a variety of different information channels about

 a single transmission channel in which each of the

 digital signals from a sequence of code units

 exists, characterized in that code units occurring simultaneously from the different information channels are represented by a common code word, so that one of the several sequences of code units

 only sequence of code words arises; that the consequence

 the code words are transmitted over the single transmission channel; that the transmitted sequence of code words

 is decoded, with each codeword transmitted

 a plurality of code units for which different information channels are generated and that the code units are supplied to associated reception-side information channels.

3Procedure for generating a frequency / phase modulation, characterized in that means are provided which relate information. convert a signal into pulse durations, either the unipolar or bipolar pulse duration rectangle being generated directly by generation via a pulse duration modulation circuit or indirectly by generation with the help of the control of an interposed electronic relay or equivalent means or directly to such a sieving means, which too

 can be replaced by the properties of the transmission path, if necessary, that the real corner pulses in sinusoidal half periods. Periods are reshaped.

 4.Method for generating a frequency modulation, characterized in that means are provided which relate information. Convert signal (Fig.30a, Inf) into pulse durations

(Eig.30b, 32) that switching means continue

for the dimensioning of the pulse durations, in particular counter switching means (Fig. 35, Z) are provided, which at the same time mark the pulse durations (eg Fig. 35,, Z, A), the marking circuits are so. in connection with pulse duration pulses via gates connected to an electronic switching means (Fig. 35, ER) that the beginning and the end of the respective pulse duration pulse encode an odic signal, in particular a square pulse, such screening means are widely provided that the line only sine-like or sinusoidal alternating currents or / and harmonics thereof. arrive (Fig. 35, fmo);

 5. A method for generating a frequency modulation, characterized in that means are provided which relate information. convert a signal into pulse durations and that switching means are also provided which convert the continuous pulses into an uninterrupted sequence (pd, Pd, Pd, ..) or the pulse duration pulses and the associated pauses (Fig. 32, PD1, P, PD2)

6. A method for color television, characterized in that all signals are combined in a code-multiplexed manner on the transmission side. B

where the color, tone and other signals can be assigned to a plurality of Y signals in a code-multiplexed manner, and that the receiving side is designed as a superimposed receiver (superheterodyne), with the decoder arranged behind the demodulator (Fig. 23, IM) with which the decoded signals: to be distributed.

7.Procedure for coding the color television signals, characterized in that the y signal, red signal in series y signal, blue signal, Y signal, tone + other signals are tapped in an uninterrupted order that the PAM values: on the half-period or Period duration from

Half waves or Periods of an alternating current are transmitted, namely in the case of amplitude equality or that only the order Y, r, Y, bl is provided and the sound and other signals by a binary or duobinary amplitude code (Eig.55) is coded in such a way that each half-wave or period is assigned an amplitude value corresponding to the code, the 4 amplitude values (Eig. 52) being code-multiplexed and assigned to different channels.

 8. A method for coding the color television signals, characterized in that the television signals are coded only with a frequency (Pig.53, 54, 66) in such a way that these serially arranged code elements, which are caused by the amplitudes of the half waves. Periods with the characteristic values large or small amplitude value or small, medium and large amplitude value are formed for all signals or that the code is formed from a large number of periods with 2 or 3 characteristics and a continuous transition between the sizes (Fig. 66, Ü), where necessary this code is provided for the accommodation of a channel in the gap between the conventional channels.

 9. Device for transmitting television signals, which a luminance signal (L), a first and a second color signal (I, Q), synchronizing signals (S) and sound signals

 (T) contains with

- A first A / D converter (L-A / D), the input of which

 analog luminance signal is supplied and at its

 Output digital luminance signal samples occur;

 - a first memory (ZSpIQ) which has an input for

 the first color signal and a second input for

 has the second color signal and signal values of these two

 Color signals save and on. a first or second

 Output provides

- A changeover switch (U4) with two inputs, with are connected to the outputs of the first memory and to an output,

a second A / D converter (A / -D, U4) whose input is coupled to the output of the first switch (U4) and to an output,

a second memory (ZSpST) with an input for the synchronization signal and a second input for the sound signal, for storing signal values of these two signals and two outputs at which the signal values are available,

a second changeover switch (U5) with two inputs, which are coupled to the outputs of the second memory and with one output,

a second A / D converter (A / D, U5) this input with the output of the second switch (U5); is coupled and with an output,

 a buffer (Sp) for storing the

 digital luminance signal samples, the alternating digital color signal samples and the alternating digital synchronization and sound signal samples, the buffer (Sp) having a first group of outputs at which the code elements of the successive digital luminance signal samples are available in parallel, with one another group of outputs at which code elements of the digital color signal samples are available and another output at which the bits of the synchronizing tone signal samples are available;

- An encoder (COD) with a first group of inputs, which are coupled to the first group of outputs of the buffer (Sp) and each to receive the bits of a digital luminance signal sample in parallel, with a second group of three inputs, each via one Switches (U1, U2, U3) are coupled to a pair of outputs of the buffer (Sp), at each of which a bit of the first or second color signal is available, and a final output which is connected to the Synchronizing signal-sound signal output of the buffer is coupled, the encoder being a code word

 delivers, which each a complete digital

 Luminance signal sample, part of a color signal sample and part of a synchronizing and

 Tone signal sample represents a pair

 successive code words two parts of a color signal sample, which together form a complete

 Color signal sample results, contains, and four successive code words a complete sample of the first color signal and a complete

 Sampling value of the second color signal and alternating

 a full sample of the synchronizing signal

 and the sound signal (Fig. 77 Fig. 78

 10. Device for receiving transmitted television signals which contain a sequence of code words,

 the multiple components of a television signal with arrangements in the input stage up to the demodulator

like a radio overlay receiver

 a demodulator for evaluating the transmitted code words a decoder (Pig.23, DC), to which the demodulated code words are fed, which has several outputs, on which the components of the television signal are connected in parallel

Are available (Fig. 23) if necessary with the interposition of storage means.

 11. Device for transmitting additional signals

 between a first television channel and a second,

 higher-frequency television channel, with screening means for generating a Nyquist edge of the television signals of the first television channel, characterized by a series resonant circuit

 to remove the television signals from a narrow

 Frequency band between the channels and an arrangement

for introducing a sinusoidal oscillation (Fig. 82, 195, 25) 12.A method according to claims 1 to 3, characterized gekennzeich¬net that the pulse duration pulses and pauses resp. If pulse duration pulses are stored in an uninterrupted sequence, control electronic switching means immediately (ERFig. 36,382, so that the respective pulse duration or pulse duration pause into a period resp. Half period of unipolar or bipolar rectangular pulses is converted and that sieving means are provided which, respectively, are sine-like half-waves from the rectangular pulses. Make periods in a continuous sequence of positive and negative half waves.

 13.Procedures for evaluating distances e.g. between pulses or of half or period durations, characterized in that at the beginning of the distance marking (Fig. 60,1) or at the zero crossing of the half-period, means for generating a sawtooth voltage are left on and that at the end of the distance marking or at the 2nd, zero crossing of the half-period (FIG. 59) means are switched to the sawtooth voltage which measure one dimension thereof or that means are provided (FET) which store this voltage in particular in a capacitor.

 14. The method according to claims 1 to 15, characterized in that multiple use of current paths takes place in such a way that several information channels are combined in a time-multiplexed manner (FIG. 56) or that the control pulses for the counter elements receive such an sequence (FIG. 57, Jm1 , Jm2) that their encoding alternating currents do not get any overlap when transmitted via a current path.

 15. The method according to claim 1, characterized in that a multi-level amplitude code (binary, duobinary, etc.) and / or one or multi-level phase ccd e and / or an analog amplitude and / or phase code is provided for the coding, which is particularly for multiple use or Reduction of the frequencies for telex (Fig: 18, 19, 20) for television (Fig. 21) for Teletex, data transmission (Fig. 24) for digital voice transmission (Fig. 28) is provided.

16. A method for the transmission of information on the basis of Quadraturaraplitudenmodulation (QAM), wherein the encoding by the amplitudes of the half-waves. Periods of an alternating current occur, characterized in that 4 channels are transmitted in the manner with only one alternating current of the same frequency, the code elements being formed by the amplitudes of the half-waves that the coding alternating currents which are arranged in phase (FIG. 10, each phase 90 degrees) difference from a to b and c to d) resp. Sampling, so in the phase position, if necessary, while temporarily storing the sampling of one or more channels for the transmission, that the channels combined to form 2 addition alternating currents (FIGS. 10, 10b / c, 10d / e) are phase-shifted with respect to one another and that these two alternating addition currents are added again (FIGS. 10, 0/90/90 /

180 degrees),

 17.Procedure for the transmission of information on the basis of quadrature amplitude modulation (QAM), the coding being determined by the amplitudes of the half-waves or Periods of an alternating current occur, characterized in that the addition alternating current is formed in such a way that the characteristic states (Fig. 11, I, II, III.) Resulting from the addition of the coding alternating currents (FIG. 11, K1 / K2, K3 / K4) , IV) to the amplitudes of an alternating current of the same frequency: are transmitted, the characteristic states (Fig. 11, II, III) not lying on the predetermined vector (Fig. 11, I) being coded on this (Fig. 11, (II ), (III),) and thus transmitted by the amplitudes of the Qüasi addition alternating current, on the receiving side the evaluation is carried out by determining the phase position of the quasi addition alternating current and by determining measuring points. 45 degrees ahead and lagging to the quasi addition alternating current , Further means are provided for assigning the coded identification states to the channels.

18.Verfalιren for the transmission of information, in particular for telecommunications systems, characterized in that for the multiple use and / or duplex traffic in the transmission of analog and / or digital: information, an alternating current of only one frequency is provided by the information to be transmitted in both directions (coming, going) by the amplitudes of the half-waves. Periods of only one alternating current are encoded and are transmitted in an uninterrupted sequence of positive and negative half-waves, the encoding alternating currents in both directions are thereby phase-shifted by 90 degrees with respect to one another, furthermore the alternating current circuits in both directions are dimensioned in this way (FIG. 25)

or provided such release agents (Fig25, G) that in

 each receiver, a reliable evaluation of the coding alternating current assigned to it takes place.

 19.The method according to claims 1 to 18, characterized in that counting switching means are provided as means for generating the square-wave pulses, with switching pulses

 (eg sine or square-wave pulses), which have an excessive frequency compared to the square-wave pulses (FIG. 7, Osz), control switching means are also provided (FIG. 7, Cod), each of which corresponds to the respective code a predetermined number of switching pulses Mark at the outputs of the counter switching means (Fig. 7, g2, G2, g3, G3) and which influence an electronic relay (Fig. 7, ER) in such a way that square-wave pulses with the coded pulse duration are sent, with alternating different potentials if necessary is assigned (Fig. 7, J).

 20. Method for the transmission of analog or digital pulse-amplitude-modulated information of two channels, characterized in that the pulses of both channels are converted into a staircase signal (Fig. 68), that furthermore 2 carriers, which are phase-shifted by 90 degrees with respect to one another, are provided with such a frequency, that they form a whole multiple compared to the sampling frequency, the staircase signal is modulated onto the assigned carrier for a predetermined number of periods, furthermore the carrier alternating currents are added and the phase shift of the total alternating current compared to a comparative alternating current (FIG. 68) is measured and one or more Periods of the comparison alternating current are added to a total period, the amplitude of the cumulative change trome is impressed on the coding half-cycle with the total period.

 21.A method according to sprühhen 1 to 6, characterized in that a duplex traffic over F unk is provided (Fig. 26) by wearden provided in a receiving point phase shifter arrangements which phase-shift the received alternating current on QAM basis for synchronization of the transmitter associated with this receiver, whereby the one determining the reception situation

 Switching means are assigned tolerances, preferably only one polarization plane being provided.