WO2000042700A1 - Bipolar chopper and method of using same - Google Patents

Bipolar chopper and method of using same Download PDF

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Publication number
WO2000042700A1
WO2000042700A1 PCT/IL2000/000026 IL0000026W WO0042700A1 WO 2000042700 A1 WO2000042700 A1 WO 2000042700A1 IL 0000026 W IL0000026 W IL 0000026W WO 0042700 A1 WO0042700 A1 WO 0042700A1
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WO
WIPO (PCT)
Prior art keywords
voltage
fraction
input voltage
load
sample
Prior art date
Application number
PCT/IL2000/000026
Other languages
French (fr)
Inventor
Prosper Dahan
Ron Kallus
Original Assignee
Dip Digital Power Systems Ag
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Dip Digital Power Systems Ag filed Critical Dip Digital Power Systems Ag
Priority to JP2000594192A priority Critical patent/JP2002535951A/en
Priority to EP00900329A priority patent/EP1149462A1/en
Priority to AU19995/00A priority patent/AU1999500A/en
Publication of WO2000042700A1 publication Critical patent/WO2000042700A1/en

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/02—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc
    • H02M5/04—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters
    • H02M5/22—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M5/275—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M5/293—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only

Definitions

  • This invention relates to electronic voltage control circuits.
  • Electronic dimmer circuits are typically based on a silicon controlled rectifier or triac which allows switching of the a.c. supply voltage at a controllable firing angle in the a.c. cycle.
  • the triac conducts current from the moment that the triac is triggered until the a.c. supply current cycle passes through zero, thereby allowing only a fraction of the a.c. supply voltage to pass.
  • the principle on which such dimmers operate is that by adjusting the firing angle, a fraction of the a.c. supply voltage is fed to the load so that the r.m.s. voltage across the load is reduced. This, in turn, reduces the power consumption of the load.
  • a drawback with such an approach is that when only a fractional voltage is fed to the load (i.e. the firing angle is greater than 0°), the load voltage is no longer sinusoidal and this both introduces undesirable harmonics and reduces the power factor.
  • the power factor is a measure of the quantity of useful power taken from the supply. If the power factor is less than unity, this means that the supply network feeds reactive power to the load and this causes undesirable phase imbalances for which the customer is heavily penalized.
  • a further drawback with conventional dimmer circuits is that, since the output voltage is derived by effectively channeling part of the input voltage through a switch, the output voltage waveform inevitably follows the input voltage waveform in shape. In practice, this means that any imperfections or noise in the input voltage waveform are reflected in the output voltage waveform.
  • a.c. input voltage supply comprising the steps of:
  • a bipolar chopper for obtaining a desired fraction of an a.c. input voltage from an a.c. voltage supply, comprises: a sampling unit for sampling the a.c. input voltage so as to produce a plurality of voltage samples during each cycle of the a.c. voltage supply, a processor coupled to the sampling unit for selecting a fraction of each said voltage sample commensurate with a desired fractional power consumption thereof, and a filter for low-pass filtering said fraction of said plurality of voltage samples.
  • voltage reduction is achieved by a desired fraction by sampling the input voltage at high frequency and passing a desired fraction of each sample to a load.
  • the average voltage across the load may be reduced by a factor of n, by feeding th l/n of the voltage samples to the load.
  • the output voltage may be selected to have an accurate predetermined waveform substantially free of any noise by first sampling the input voltage at high frequency. For each voltage sample, a departure of the instantaneous voltage of the respective voltage sample from the desired voltage magnitude allows a commensurate fraction of the voltage sample to be output. This produces a clean sinusoidal waveform for the output voltage and preserves near unity power factor.
  • the desired voltage magnitude of each sample may be determined from a knowledge of the voltage waveform V(t) of the output voltage and the instantaneous time of the current voltage sample. By such means, a substantially pure sinusoidal output voltage may be produced regardless of the shape of the input voltage.
  • Fig. 1 is a block diagram of a voltage reducer according to the invention
  • Fig. 2 shows schematically a driver circuit for fast switching of the P M signals to the low pass filter in the voltage reducer shown in Fig. 1 ;
  • Fig. 3 shows graphically voltage waveforms of the a.c. input voltage
  • Figs. 4a and 4b show graphically voltage waveforms of the reduced 5 output voltage at a fraction equal to 50% of the input voltage
  • Figs. 4a and 4b show graphically voltage waveforms of the reduced output voltage at a fraction equal to 50% of the input voltage
  • Figs. 5a and 5b show graphically voltage waveforms of the reduced output voltage at a fraction equal to 80% of the input voltage; 0 Figs. 6a and 6b show graphically voltage waveforms of the reduced output voltage at a fraction equal to 20% of the input voltage.
  • Fig. 1 shows a block diagram of a voltage reducer depicted generally as 10 for obtaining a desired fraction of an a.c. input voltage 11 derived from 5 an a.c. voltage supply (not shown).
  • the voltage reducer 10 comprises a central processing unit (CPU) 12 to which there is coupled a voltage sensor 13 for sensing the a.c. input voltage 11.
  • a zero cross detector 14 is coupled to the voltage sensor 13 and to the CPU 12 for producing a trigger signal when the a.c. input voltage climbs upward through zero.
  • the voltage reducer 10 comprises a central processing unit (CPU) 12 to which there is coupled a voltage sensor 13 for sensing the a.c. input voltage 11.
  • a zero cross detector 14 is coupled to the voltage sensor 13 and to the CPU 12 for producing a trigger signal when the a.c. input voltage climbs upward through zero.
  • the voltage reducer 10 comprises a central processing unit (CPU) 12 to which there is coupled a voltage sensor 13 for sensing the a.c. input
  • a sampling unit 15 for sampling the a.c. input voltage so as to produce a plurality of voltage samples during each cycle of the a.c. voltage supply.
  • the time between successive samples allows computation of the supply frequency which, in turn, allows determination of the sampling points.
  • the 25 16 includes a keypad 17 and a display 18 and allows a user to set an output voltage 19 to a desired fraction of the input voltage 11.
  • the CPU 12 is responsively coupled to the user interface 16 for selecting the same fraction of the plurality of voltage samples commensurate with the desired fractional power consumption thereof set by the user.
  • PWM pulse-width modulated
  • the PWM signals have constant height indicative of logic HIGH or LOW but have different widths corresponding to the amplitude of the respective output voltage requested.
  • the PWM pulses are fed to a power unit 21, which alternately switches a pair of bipolar a.c. switches at the sampling frequency. This is explained in detail below with reference to Figs. 4, 5 and 6 of the drawings.
  • a DMX 512 input 22 is coupled to the CPU 12 and allows the unit to be connected as one of up to 512 remote devices via an RS485 network.
  • Each device in the network has a unique address allowing a specific device to be accessed by sending a control byte corresponding to the address of the desired device.
  • a digital control byte having a value from 0 to 255 and being representative of the desired voltage reduction, may be sent through the RS485 network to the device.
  • An analog voltage unit 23 coupled to the CPU 12 allows a d.c. voltage to be fed to the CPU 12 representative of the desired voltage reduction.
  • the d.c. voltage may extend from 0 to 10 N d.c. corresponding to zero to full voltage a.c.
  • the CPU 12 will control the a.c. output voltage 19 so as to be equal to 120 N a.c.
  • a current limiter 24 limits the current consumption according to the preset maximum requested by the user.
  • the sampling unit 15 samples both the input voltage and the current consumed by the load, and checks that each sampled power slice is within its predetermined rating.
  • the current limiter 24 is hardware programmed to sense each high frequency sample and makes allowance for the fact that typically on startup, current ⁇ RU S H may considerably exceed the nominal current rating.
  • Fig. 2 shows a detail of the power unit 21 which comprises a pair of bipolar a.c. MOSFET switches 37 and 38, having a common junction 39, for switching the a.c. power between the load and the neutral feeder, in accordance with the PWM signal. The desired switching is effected by a
  • PWM control unit 43 which is synchronized to the a.c. input voltage 11 and includes a pair of precisely synchronized anti-phase outputs 44 and 45 having logic levels which invert continuously at the sampling frequency for opening and closing the bipolar a.c. MOSFET switches 37 and 38 so that the desired fraction of the a.c. input voltage is fed, via the junction 39 of the bipolar a.c. o MOSFET switches 37 and 38, to the low pass filter 40.
  • the a.c. input voltage 11 is derived from a main a.c. supply having a nominally sinusoidal waveform and the sampling frequency is as high as lOOKHz giving a very large number of samples.
  • Fig. 3 shows graphically the waveform of the a.c. input voltage 11 5 having positive and negative half cycles 30 and 31 , respectively.
  • Fig. 4a shows graphically the corresponding output voltage 50 produced at the junction 39 between the two bipolar a.c. MOSFET switches 37 and 38 in the power unit 21 and having an r.m.s. value equal to 50% of the input voltage 11.
  • the continuous curve 51 represents the voltage waveform 0 after filtering by the low pass filter 40.
  • Fig. 4b shows graphically the output voltage 50 shown in Fig. 4a at much expanded time scale. It may be seen that only 50% of each voltage sample is fed through the two bipolar a.c. MOSFET switches 37 and 38 to the low pass filter 40.
  • 5 Figs. 5a and 5b show graphically the corresponding output voltage 50 at normal and expanded time scales when the output voltage is required to be equal to 80% of the input voltage. It will be noticed clearly from Fig. 5b that the proportion of each voltage sample which is fed through the two bipolar a.c. MOSFET switches 37 and 38 to the low pass filter 40 is much greater than 0 the proportion which is not passed through the switches.
  • Figs. 5b shows graphically the output voltage 50 shown in Fig. 4a at much expanded time scale. It may be seen that only 50% of each voltage sample is fed through the two bipolar a.c. MOSFET switches 37 and 38 to the low pass filter 40.
  • FIG. 6a and 6b show graphically the corresponding output voltage 50 at normal and expanded time scales when the output voltage is required to be equal to 20% of the input voltage. It will be noticed clearly from Fig. 6b that, in this case, the proportion of each voltage sample which is fed through the 5 two bipolar a.c. MOSFET switches 37 and 38 to the low pass filter 40 is much less than the proportion which is not passed through the switches.
  • DSP Digital Signal Processor

Abstract

A method and a bipolar chopper for obtaining an output voltage from an a.c. input voltage supply, by continuously sampling the a.c. input voltage so as to produce a plurality of voltage samples during each cycle of the a.c. input voltage supply, selecting a fraction of each said voltage sample commensurate with a desired fractional power consumption thereof, and low-passing filtering said fraction of each said voltage sample. According to a preferred embodiment, the output voltage is sinusoidal and, for each voltage sample, a departure of the instantaneous voltage of the respective voltage sample from the desired voltage magnitude allows a commensurate fraction of the voltage sample to be output. This produces a clean sinusoidal waveform for the output voltage and preserves near unity power factor.

Description

Bipolar chopper and method of using same
FIELD OF THE INVENTION
This invention relates to electronic voltage control circuits.
BACKGROUND OF THE INVENTION
Electronic dimmer circuits are typically based on a silicon controlled rectifier or triac which allows switching of the a.c. supply voltage at a controllable firing angle in the a.c. cycle. By such means, the triac conducts current from the moment that the triac is triggered until the a.c. supply current cycle passes through zero, thereby allowing only a fraction of the a.c. supply voltage to pass. The principle on which such dimmers operate is that by adjusting the firing angle, a fraction of the a.c. supply voltage is fed to the load so that the r.m.s. voltage across the load is reduced. This, in turn, reduces the power consumption of the load.
A drawback with such an approach is that when only a fractional voltage is fed to the load (i.e. the firing angle is greater than 0°), the load voltage is no longer sinusoidal and this both introduces undesirable harmonics and reduces the power factor. In particular, the power factor is a measure of the quantity of useful power taken from the supply. If the power factor is less than unity, this means that the supply network feeds reactive power to the load and this causes undesirable phase imbalances for which the customer is heavily penalized. A further drawback with conventional dimmer circuits is that, since the output voltage is derived by effectively channeling part of the input voltage through a switch, the output voltage waveform inevitably follows the input voltage waveform in shape. In practice, this means that any imperfections or noise in the input voltage waveform are reflected in the output voltage waveform.
SUMMARY OF THE INVENTION
It is an object of the invention to provide a bipolar chopper wherein the r.m.s. a.c. voltage across a load may be controlled without derogating from the shape of the supply voltage, and at the same time cleaning any noise.
It is a further object of the invention to provide such a bipolar chopper for reducing the average voltage across a load.
According to the invention there is provided a method for obtaining a desired shape of an output voltage from an a.c. input voltage supply, said method comprising the steps of:
(a) continuously sampling the a.c. input voltage so as to produce a plurality of voltage samples during each cycle of the a.c. input voltage supply,
(b) selecting a fraction of each said voltage sample commensurate with a desired fractional power consumption thereof, and
(c) low-passing filtering said fraction of each said voltage sample.
In accordance with the invention, a bipolar chopper for obtaining a desired fraction of an a.c. input voltage from an a.c. voltage supply, comprises: a sampling unit for sampling the a.c. input voltage so as to produce a plurality of voltage samples during each cycle of the a.c. voltage supply, a processor coupled to the sampling unit for selecting a fraction of each said voltage sample commensurate with a desired fractional power consumption thereof, and a filter for low-pass filtering said fraction of said plurality of voltage samples.
Seeing that the output voltage is of substantially ideal sinusoidal shape, near unity power factor exceeding 0.99 is achieved when the input voltage is derived from an a.c. electrical supply having sinusoidal waveform.
According to a first embodiment of the invention, voltage reduction is achieved by a desired fraction by sampling the input voltage at high frequency and passing a desired fraction of each sample to a load. For example, the average voltage across the load may be reduced by a factor of n, by feeding th l/n of the voltage samples to the load.
According to a second embodiment of the invention, the output voltage may be selected to have an accurate predetermined waveform substantially free of any noise by first sampling the input voltage at high frequency. For each voltage sample, a departure of the instantaneous voltage of the respective voltage sample from the desired voltage magnitude allows a commensurate fraction of the voltage sample to be output. This produces a clean sinusoidal waveform for the output voltage and preserves near unity power factor. The desired voltage magnitude of each sample may be determined from a knowledge of the voltage waveform V(t) of the output voltage and the instantaneous time of the current voltage sample. By such means, a substantially pure sinusoidal output voltage may be produced regardless of the shape of the input voltage.
BRIEF DESCRIPTION OF THE DRAWINGS
In order to understand the invention and to see how it may be carried out in practice, a preferred embodiment will now be described, by way of non-limiting example only, with reference to the accompanying drawings, in which:
Fig. 1 is a block diagram of a voltage reducer according to the invention; Fig. 2 shows schematically a driver circuit for fast switching of the P M signals to the low pass filter in the voltage reducer shown in Fig. 1 ;
Fig. 3 shows graphically voltage waveforms of the a.c. input voltage;
Figs. 4a and 4b show graphically voltage waveforms of the reduced 5 output voltage at a fraction equal to 50% of the input voltage;
Figs. 4a and 4b show graphically voltage waveforms of the reduced output voltage at a fraction equal to 50% of the input voltage;
Figs. 5a and 5b show graphically voltage waveforms of the reduced output voltage at a fraction equal to 80% of the input voltage; 0 Figs. 6a and 6b show graphically voltage waveforms of the reduced output voltage at a fraction equal to 20% of the input voltage.
DETAILED DESCRIPTION OF A PREFERRED EMBODIMENT
Fig. 1 shows a block diagram of a voltage reducer depicted generally as 10 for obtaining a desired fraction of an a.c. input voltage 11 derived from 5 an a.c. voltage supply (not shown). The voltage reducer 10 comprises a central processing unit (CPU) 12 to which there is coupled a voltage sensor 13 for sensing the a.c. input voltage 11. Likewise, a zero cross detector 14 is coupled to the voltage sensor 13 and to the CPU 12 for producing a trigger signal when the a.c. input voltage climbs upward through zero. The voltage
20 sensor 13 in combination with the zero cross detector 14 constitute a sampling unit 15 for sampling the a.c. input voltage so as to produce a plurality of voltage samples during each cycle of the a.c. voltage supply. The time between successive samples allows computation of the supply frequency which, in turn, allows determination of the sampling points. A user interface
25 16 includes a keypad 17 and a display 18 and allows a user to set an output voltage 19 to a desired fraction of the input voltage 11. The CPU 12 is responsively coupled to the user interface 16 for selecting the same fraction of the plurality of voltage samples commensurate with the desired fractional power consumption thereof set by the user. At an output of the CPU 12 are pulse-width modulated (PWM) signals whose widths are proportional to the respective requested portion of the input voltage, sampled by the CPU 12. Specifically, the PWM signals have constant height indicative of logic HIGH or LOW but have different widths corresponding to the amplitude of the respective output voltage requested. The PWM pulses are fed to a power unit 21, which alternately switches a pair of bipolar a.c. switches at the sampling frequency. This is explained in detail below with reference to Figs. 4, 5 and 6 of the drawings.
A DMX 512 input 22 is coupled to the CPU 12 and allows the unit to be connected as one of up to 512 remote devices via an RS485 network. Each device in the network has a unique address allowing a specific device to be accessed by sending a control byte corresponding to the address of the desired device. By this means, a digital control byte having a value from 0 to 255 and being representative of the desired voltage reduction, may be sent through the RS485 network to the device. Thus, if the input voltage is 240N a.c. and the control byte is equal to 127, then the CPU 12 will control the a.c. output voltage 19 so as to be equal to 120N a.c.
An analog voltage unit 23 coupled to the CPU 12 allows a d.c. voltage to be fed to the CPU 12 representative of the desired voltage reduction. For example, the d.c. voltage may extend from 0 to 10 N d.c. corresponding to zero to full voltage a.c. Thus, if the input voltage is 240 N a.c. and the d.c. voltage level of the analog voltage unit 23 is 5N d.c, then the CPU 12 will control the a.c. output voltage 19 so as to be equal to 120 N a.c.
A current limiter 24 limits the current consumption according to the preset maximum requested by the user. The sampling unit 15 samples both the input voltage and the current consumed by the load, and checks that each sampled power slice is within its predetermined rating. The current limiter 24 is hardware programmed to sense each high frequency sample and makes allowance for the fact that typically on startup, current ΪRUSH may considerably exceed the nominal current rating. Fig. 2 shows a detail of the power unit 21 which comprises a pair of bipolar a.c. MOSFET switches 37 and 38, having a common junction 39, for switching the a.c. power between the load and the neutral feeder, in accordance with the PWM signal. The desired switching is effected by a
5 PWM control unit 43 which is synchronized to the a.c. input voltage 11 and includes a pair of precisely synchronized anti-phase outputs 44 and 45 having logic levels which invert continuously at the sampling frequency for opening and closing the bipolar a.c. MOSFET switches 37 and 38 so that the desired fraction of the a.c. input voltage is fed, via the junction 39 of the bipolar a.c. o MOSFET switches 37 and 38, to the low pass filter 40.
In practice, the a.c. input voltage 11 is derived from a main a.c. supply having a nominally sinusoidal waveform and the sampling frequency is as high as lOOKHz giving a very large number of samples.
Fig. 3 shows graphically the waveform of the a.c. input voltage 11 5 having positive and negative half cycles 30 and 31 , respectively.
Fig. 4a shows graphically the corresponding output voltage 50 produced at the junction 39 between the two bipolar a.c. MOSFET switches 37 and 38 in the power unit 21 and having an r.m.s. value equal to 50% of the input voltage 11. The continuous curve 51 represents the voltage waveform 0 after filtering by the low pass filter 40.
Fig. 4b shows graphically the output voltage 50 shown in Fig. 4a at much expanded time scale. It may be seen that only 50% of each voltage sample is fed through the two bipolar a.c. MOSFET switches 37 and 38 to the low pass filter 40. 5 Figs. 5a and 5b show graphically the corresponding output voltage 50 at normal and expanded time scales when the output voltage is required to be equal to 80% of the input voltage. It will be noticed clearly from Fig. 5b that the proportion of each voltage sample which is fed through the two bipolar a.c. MOSFET switches 37 and 38 to the low pass filter 40 is much greater than 0 the proportion which is not passed through the switches. Figs. 6a and 6b show graphically the corresponding output voltage 50 at normal and expanded time scales when the output voltage is required to be equal to 20% of the input voltage. It will be noticed clearly from Fig. 6b that, in this case, the proportion of each voltage sample which is fed through the 5 two bipolar a.c. MOSFET switches 37 and 38 to the low pass filter 40 is much less than the proportion which is not passed through the switches.
Whilst the invention has been described with particular regard to the fractional reduction of an a.c. supply voltage having a sinusoidal waveform, it will be appreciated that the principles of the invention may also be applied to o voltages having other waveforms.
It will also be appreciated that whilst a particular embodiment relating to digital processing has been described, the PWM control and associated circuitry are not essential features of the invention. Thus, any other circuit for passing a desired number of pulse samples to the low pass filter will also 5 suffice.
Likewise, it will be appreciated that the components shown functionally in the block diagram of the voltage reducer 10, apart from the power unit 21, may be constituted by a suitable Digital Signal Processor (DSP).

Claims

CLAIMS:
1. A method for obtaining a desired shape of an output voltage from an a.c. input voltage supply, said method comprising the steps of:
(a) continuously sampling the a.c. input voltage so as to produce a plurality of voltage samples during each cycle of the a.c. input voltage supply,
(b) selecting a fraction of each said voltage sample commensurate with a desired fractional power consumption thereof, and
(c) low-passing filtering said fraction of each said voltage sample.
2. The method according to Claim 1, wherein said fraction is Vn and step (b) includes selecting a n fraction of the voltage sample.
3. The method according to Claim 1 or 2, further including the step of
(d) connecting the desired fraction of the a.c. voltage to a load,
(e) monitoring the voltage across the load, and (f) interrupting the a.c. voltage to the load upon an unacceptable departure from a specified reference of current limit.
4. The method according to Claim 3, further including the step of:
(g) automatically re-connecting the a.c. voltage to the load a predetermined time interval after interruption thereof.
5. The method according to Claim 4, wherein steps (f) and (g) include the steps of: i) alternately opening and closing at high frequency a pair of polarized anti-phase switches each for feeding the a.c. input voltage to a load during respective positive and negative half cycles of the a.c. input voltage, and ii) adjusting an average time during which said switches are open and closed during each voltage sample so that said fraction of the respective voltage sample is passed to the load.
6. The method according to Claim 5, further including: iii) returning a remaining fraction of the voltage samples to the a.c. input voltage supply so as to improve efficiency and save energy.
7. The method according to any one of claims 3 to 6, wherein the output voltage is of a known function V(t) and step (b) includes: i) measuring a corresponding magnitude of said fraction of each said voltage sample at an instantaneous time t relative to a known time origin of the a.c. input voltage, ϋ) determining from said function V(t) a magnitude of the output voltage at said instantaneous time t; and iii) selecting said fraction of the respective voltage sample commensurate with a ratio between the respective instantaneous magnitudes of said fraction and the output voltage.
8. The method according to Claim 7, wherein step (iii) includes the steps of:
(A) alternately opening and closing at high frequency a pair of polarized anti-phase switches each for feeding the a.c. input voltage to a load during respective positive and negative half cycles of the a.c. input voltage, and
(B) adjusting an average time during which said switches are open and closed during each voltage sample so that said fraction of the respective voltage sample is passed to the load.
9. The method according to Claim 8, further including:
(C) returning a remaining fraction of the voltage samples to the a.c. input voltage supply so as to improve efficiency and save energy.
10. The method according to any one of the preceding claims, wherein the a.c. voltage is sampled at a frequency exceeding 10kHz.
11. The method according to any one of the preceding claims, wherein the a.c. input voltage has a nominally sinusoidal waveform.
12. The method according to Claim 11, wherein the output voltage has a nominally sinusoidal waveform.
13. A bipolar chopper for obtaining a desired fraction of an a.c. input voltage from an a.c. voltage supply, said bipolar chopper comprising: a sampling unit for sampling the a.c. input voltage so as to produce a plurality of voltage samples during each cycle of the a.c. voltage supply, a processor coupled to the sampling unit for selecting a fraction of each said voltage sample commensurate with a desired fractional power consumption thereof, and a filter for low-pass filtering said fraction of said plurality of voltage samples.
14. The bipolar chopper according to Claim 13, wherein said fraction is l/« and the processor is adapted to pass 1/n of the energy of each said voltage sample to the load.
15. The bipolar chopper according to Claim 13 or 14, wherein the processor includes a driver circuit for feeding said fraction of the a.c. voltage to a load, and returning a remaining fraction of the voltage samples to the a.c. input voltage supply.
16. The bipolar chopper according to Claim 15, wherein the driver circuit comprises: a pair of polarized bipolar a.c. switches for switching alternately between the load and a return feeder of the a.c. input voltage supply so as to feed the a.c. input voltage to the load during respective positive and negative half cycles of the a.c. input voltage, and a PWM control synchronized to the a.c. input voltage and including a pair of anti-phase outputs having logic levels which invert continuously at the sampling frequency for opening and closing said bipolar a.c. switches.
17. The bipolar chopper according to any one of claims 13 to 16, wherein the output voltage is of a known function V(t) and the processor is adapted to: i) measure a corresponding magnitude of said fraction of each said voltage sample at an instantaneous time / relative to a known time origin of the a.c. input voltage, ii) determine from said function V(t) a magnitude of the output voltage at said instantaneous time t; and iii) select said fraction of the respective voltage sample commensurate with a ratio between the respective instantaneous magnitudes of said fraction and the output voltage.
18. The bipolar chopper according to Claim 17, wherein the driver circuit is responsive to the processor for:
(A) alternately opening and closing at high frequency a pair of polarized anti-phase switches each for feeding the a.c. input voltage to a load during respective positive and negative half cycles of the a.c. input voltage, and
(B) adjusting an average time during which said switches are open and closed during each voltage sample so that said fraction of the respective voltage sample is passed to the load.
19. The bipolar chopper according to Claim 18, wherein the driver circuit is further adapted to return a remaining fraction of the voltage samples to the a.c. input voltage supply so as to improve efficiency and save energy..
20. The bipolar chopper according to Claim 13, wherein: the desired fraction of the a.c. input voltage is connected to a load. the processor is adapted to monitor the voltage across the load, and a switch is operatively coupled to the processor for interrupting the a.c. input voltage to the load upon an unacceptable departure from a specified reference current limit.
21. The bipolar chopper according to Claim 20, wherein the processor is adapted to resume normal operation, a predetermined time interval after interruption of the output voltage.
22. The bipolar chopper according to Claim 21, further including a manual selector for manually setting said predetermined time interval.
23. The bipolar chopper according to any one of Claims 13 to 22, having a manual set switch coupled to the processor for setting the desired fractional power consumption.
24. The bipolar chopper according to any one of Claims 13 to 22, having a digital control input coupled to the processor for feeding thereto a digital control signal having a value representative of the desired fractional power consumption.
25. The bipolar chopper according to Claim 24, being connected to a network so as to be remotely addressable, thereby allowing the control signal to be sent to the digital control input via the network.
26. The bipolar chopper according to any one of Claims 13 to 22, having an analog input coupled to the processor for feeding thereto a voltage having a magnitude which is representative of the desired fractional power consumption.
PCT/IL2000/000026 1999-01-14 2000-01-13 Bipolar chopper and method of using same WO2000042700A1 (en)

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Application Number Priority Date Filing Date Title
JP2000594192A JP2002535951A (en) 1999-01-14 2000-01-13 Bipolar chopper and method of using the same
EP00900329A EP1149462A1 (en) 1999-01-14 2000-01-13 Bipolar chopper and method of using same
AU19995/00A AU1999500A (en) 1999-01-14 2000-01-13 Bipolar chopper and method of using same

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Application Number Priority Date Filing Date Title
IL128045 1999-01-14
IL12804599A IL128045A0 (en) 1999-01-14 1999-01-14 Method and device for obtaining a fractional voltage from an a.c. voltage source

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US9730890B2 (en) 2003-07-10 2017-08-15 Mylan Pharmaceuticals, Inc. Bronchodilating beta-agonist compositions and methods

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Publication number Priority date Publication date Assignee Title
US9730890B2 (en) 2003-07-10 2017-08-15 Mylan Pharmaceuticals, Inc. Bronchodilating beta-agonist compositions and methods
DE102006029502A1 (en) * 2006-06-27 2008-01-03 Lite Puter Enterprise Co., Ltd., Sijhih Sine wave light-adjusting apparatus for lamp, has negative semi-period flywheel unit, connected with energy-storing unit and lighting unit, which is controlled by microprocessor to conduct during negative semi-period of sine wave voltage

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EP1149462A1 (en) 2001-10-31

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