WO2016167146A1 - Sine wave multiplication device and input device having same - Google Patents

Abstract

Provided is a sine wave multiplication device of simple configuration, broad input signal level range, and minimal fluctuation in characteristics due to temperature. A signal component that corresponds to the product of an input signal Si and the third harmonic of a first square wave W1 included in an output signal Su1; and a signal component that corresponds to the product of the input signal Si and the fifth harmonic of the first square wave W1 is canceled by: a signal component that corresponds to the product of the input signal Su1 and the fundamental wave of a second square wave W2 included in an output signal Su2; and a signal component that corresponds to the product of the input signal Si and the fundamental wave of a second square wave W3 included in an output signal Su3.

Description

Sine wave multiplier and input device having the same

The present invention relates to a sine wave multiplier that multiplies an input signal by a sine wave, and an input device having the sine wave multiplier.

When multiplying an input signal by a sine wave, a method using an analog multiplier such as a Gilbert cell is generally used (see Patent Document 1 below).

JP 2000-315919 A

The Gilbert cell type analog multiplier has been put into practical use, for example, with the configuration shown in FIG. When the Gilbert cell is composed of bipolar transistors, the thermal voltage VT is included as a coefficient in the multiplication result, as shown in the equations (14) and (20) of Patent Document 1. The thermal voltage VT is expressed by “k · T / q”, where k is a Boltzmann constant, T is an absolute temperature, and q is an elementary charge of an electron. Therefore, the multiplication result of the Gilbert cell, that is, the output voltage changes depending on the temperature. The same applies to other analog multipliers composed of MOS transistors. Further, in the analog multiplier, it is necessary to limit the range of the input voltage in order to ensure the multiplication accuracy due to the nonlinearity of the input / output characteristics of the transistor. For this reason, for example, when an analog multiplier is used in a capacitance type input device, securing a dynamic range of a signal and fluctuation due to temperature are problems.

Also, when sine wave multiplication is performed using an analog multiplier, it is necessary to generate a sine wave separately. Therefore, for example, in order to perform high-precision signal extraction by multiplying the input signal by a sine wave, it is necessary to generate a high-precision sine wave, which increases the circuit scale for generating a sine wave and reduces power consumption. There is a problem that increases.

The present invention has been made in view of such circumstances, and an object of the present invention is to provide a sine wave multiplication device having a simple configuration, a wide range of input signal levels, and a small variation in characteristics due to temperature.

A first aspect of the present invention relates to a sine wave multiplier that multiplies an input signal by a sine wave having a predetermined frequency. The sine wave multiplication device includes a plurality of square wave multiplication units that multiply the input signal by square waves having different frequencies, and a signal synthesis unit that synthesizes output signals of the plurality of square wave multiplication units. The square wave can be approximated as the sum of a fundamental wave that is a sine wave having the lowest frequency and a plurality of harmonics that are sine waves each having an integer multiple of the fundamental wave. The plurality of square wave multiplication units include one first square wave multiplication unit and one or more second square wave multiplication units. The first square wave multiplier multiplies the input signal by a first square wave having the sine wave of the predetermined frequency as the fundamental wave. The second square wave multiplication unit is a second square wave having the fundamental wave as a sine wave equal to one harmonic included in the first square wave or a sine wave obtained by inverting the phase of the one harmonic. Is multiplied by the input signal. The signal synthesis unit converts a signal component corresponding to a product of at least one harmonic of the first square wave included in the output signal of the first square wave multiplication unit and the input signal into the second square wave. The signal is canceled by a signal component corresponding to the product of the fundamental wave of the second square wave and the input signal included in the output signal of the multiplier.

According to the above configuration, a signal component corresponding to a product of at least one harmonic of the first square wave and the input signal included in the output signal of the first square wave multiplier is the second square wave. The signal is canceled by a signal component corresponding to the product of the fundamental wave of the second square wave and the input signal included in the output signal of the wave multiplier. Therefore, in the signal resulting from the synthesis by the signal synthesis unit, the signal component corresponding to the product of the harmonic of the first square wave and the input signal is reduced, and the fundamental wave of the first square wave (the A signal component corresponding to a product of a sine wave having a predetermined frequency and the input signal becomes a dominant component.
In the sine wave multiplication device, the square wave multiplication unit is used to multiply the sine wave (the fundamental wave of the first square wave) and the input signal. Less susceptible to fluctuations, and changes in characteristics due to temperature are small. Further, the use of the square wave multiplication unit makes it difficult to be affected by the input / output nonlinear characteristics of the transistor as in the case of an analog multiplier, so that the range of the level of the input signal is widened.
Further, in the sine wave multiplication device, the sine wave generator can be omitted by using the square wave multiplication unit, so that the circuit configuration is simplified.

Preferably, the square wave multiplication unit generates an output signal proportional to the input signal in each of one half cycle and the other half cycle in one cycle of the square wave multiplied by the input signal, and The output signal may be generated such that the absolute value of the ratio between the input signal and the output signal is equal in one half cycle and the other half cycle, and the sign of the ratio is inverted.
Thereby, in the square wave multiplication unit, the absolute value of the ratio between the input signal and the output signal is the same in one half cycle and the other half cycle in one cycle of the square wave multiplied by the input signal. The output signal is generated so that the sign of the ratio is inverted. That is, the input signal and the square wave are multiplied by inverting the sign of each square wave half cycle while maintaining the absolute value of the ratio of the output signal to the input signal. Therefore, unlike an analog multiplier, it is difficult to be influenced by the temperature characteristics and input / output nonlinear characteristics of the transistor.

Preferably, the square wave multiplication unit is a charge that accumulates a charge proportional to the voltage of the input signal in each of one half cycle and the other half cycle of the square wave multiplied by the input signal. The operation and the charge output operation of outputting the charge accumulated by the charging operation to the signal synthesizer are alternately repeated at a predetermined sampling period, and the half cycle and the other half cycle, The charging operation and the charge output operation may be performed so that the ratio between the voltage of the input signal and the amount of charge accumulated by the charging operation is equal, and the polarity of the charge output to the signal synthesis unit is inverted. The signal synthesis unit responds to the sum of the charges output from the plurality of square wave multiplication units by the charge output operation each time the charge output operation is performed a predetermined number of times in the plurality of square wave multiplication units. A signal may be generated.

Preferably, the first square wave multiplication unit and the second square wave multiplication unit may include at least one capacitor that accumulates electric charge in the charging operation. In this case, the capacitance of the capacitor in which the first square wave multiplication unit accumulates electric charge in the charging operation, and the capacitance of the capacitor in which the second square wave multiplication unit accumulates electric charge in the charging operation Is a value corresponding to a ratio between the amplitude of the fundamental wave of the first square wave and the amplitude of the harmonic wave of the first square wave having the same frequency as the fundamental wave of the second square wave. You may have.

According to the above configuration, the ratio of the charge output from the first square wave multiplication unit and the charge output from the second square wave multiplication unit in the charge output operation is equal to that of the first square wave multiplication unit. It has a value corresponding to the ratio between the capacitance of the capacitor and the capacitance of the capacitor of the second square wave multiplier. And the ratio of the capacitance is the amplitude of the fundamental wave of the first square wave and the amplitude of the harmonic wave of the first square wave having the same frequency as the fundamental wave of the second square wave. It has a value according to the ratio. Therefore, the signal output from the first square wave multiplication unit and the charge output from the second square wave multiplication unit are added together in the signal synthesis unit, so that the harmonics of the first square wave and the The signal component corresponding to the product of the input signal can be canceled by the signal component corresponding to the product of the fundamental wave of the second square wave and the input signal.
Further, since the capacitance ratio of the capacitor is hardly affected by variations due to temperature and manufacturing process, the signal components can be accurately canceled.

Preferably, the sine wave multiplier may include an input node to which the input signal is input and an output node to which outputs of the plurality of square wave multipliers are connected in common.
The square wave multiplication unit connects one end of the first capacitor to the input node in one half cycle of the first capacitor and the second capacitor, and one cycle of the square wave multiplied by the input signal. A charge operation for connecting the other end of the first capacitor to a reference potential; and a charge output for connecting the one end of the first capacitor to the output node and for connecting the other end of the first capacitor to the reference potential. In the first switch unit that alternately repeats the operation in the sampling period, and in the other half cycle of the square wave that multiplies the input signal, one end of the second capacitor is connected to the input node. A charging operation for connecting the other end of the second capacitor to the reference potential; and the other end of the second capacitor connected to the output node. May have a second switch section for repeating the charge output operation for connecting said one end of said second capacitor to said reference potential alternately at the sampling period with connecting.
The signal synthesizer sets the voltage at the other terminal of the third capacitor so that a voltage difference between the third capacitor having one terminal connected to the output node and the output node and the reference potential is zero. An amplifier circuit to be controlled and a discharge circuit that discharges the charge accumulated in the third capacitor each time the charge output operation is performed a predetermined number of times in the plurality of square wave multipliers.

Preferably, the first switch unit includes a first switch element provided in a current path between the input node and the one end of the first capacitor, and the one end of the first capacitor and the output node. And a second switch element provided in a current path therebetween.
The other end of the first capacitor may be connected to the reference potential.
The second switch unit includes a third switch element provided in a current path between the input node and the one end of the second capacitor, and between the other end of the second capacitor and the reference potential. A fourth switch element provided in a current path, a fifth switch element provided in a current path between the other end of the second capacitor and the output node, the one end of the second capacitor, and the reference And a sixth switch element provided in a current path between the potential.
In one half cycle of the square wave multiplied by the input signal, the first switch element is turned on and the other switch elements are turned off during the charging operation, and the charge output operation is performed. In addition, the second switch element may be turned on and the other switch elements may be turned off.
In the other half cycle of the square wave multiplied by the input signal, the third switch element and the fourth switch element are turned on and the other switch elements are turned off during the charging operation. During the charge output operation, the fifth switch element and the sixth switch element may be turned on and the other switch elements may be turned off.

The square wave multiplication unit may include a fourth capacitor provided in a current path between the first switch element and the input node.
The first switch unit includes a seventh switch element provided in a current path between one end of the fourth capacitor and the input node, and a current path between the one end of the fourth capacitor and the reference potential. And an ninth switch element provided in a current path between the other end of the fourth capacitor and the reference potential.
The seventh switch element may be turned on / off under the same conditions as the first switch element.
The eighth switch element and the ninth switch element may be turned on / off under the same conditions as the second switch element.

Preferably, the sine wave multiplier is a noise component included in the input signal input to the plurality of square wave multipliers, from a frequency that is an integral multiple of the sampling frequency to the signal band of the input signal. A first low-pass filter that attenuates the noise component that may cause aliasing noise may be provided.
Thereby, the aliasing noise in the signal generated in the signal synthesis unit is reduced.

Preferably, the square wave multiplication unit inputs the input signal and an inverted input signal in which the polarity of the input signal is inverted, and in one half cycle of one cycle of the square wave to multiply the input signal, the input An output signal proportional to the signal at a predetermined ratio may be generated, and an output signal proportional to the inverted input signal at the predetermined ratio may be generated in the other half cycle of the one cycle.
For example, the square wave multiplier generates an output current proportional to the voltage of the input signal at a predetermined ratio in one half cycle of the square wave multiplied by the input signal, and the other in the one cycle. In this half cycle, an output current proportional to the voltage of the inverted input signal at the predetermined ratio may be generated. The signal synthesis unit may generate a signal corresponding to the sum of the output currents output from the plurality of square wave multiplication units.

Preferably, the sine wave multiplication device has N patterns of the second squares corresponding to the first to Nth harmonics in order of decreasing frequency among the harmonics included in the first square wave. N harmonic wave multipliers for multiplying the input signal by a wave, and the harmonics included in the first square wave from signals output as a result of synthesis in the signal synthesis unit, the frequency being the frequency There may be a second low-pass filter that attenuates the (N + 1) th and higher harmonics in order of increasing.
Thereby, the signal component corresponding to the harmonics of the first square wave is reduced in the signal generated in the signal synthesis unit.

A second aspect of the present invention relates to an input device that inputs information according to the proximity of an object. This input device multiplies a DC signal by a sine wave having a predetermined frequency and a sensor unit including a sensor element whose capacitance changes in accordance with the proximity of the object, and as a result of the multiplication, A first sine wave multiplier for outputting a first sine wave; and a sine wave drive voltage corresponding to the first sine wave is applied to the sensor element, and the current flowing in the sensor element is applied by the application of the drive voltage. A detection signal generation unit that generates a detection signal, a second sine wave multiplication unit that multiplies the detection signal by a second sine wave having the predetermined frequency, and a signal obtained by multiplying the second sine wave multiplication unit by direct current. A low-pass filter for extracting components. The first sine wave multiplier and the second sine wave multiplier are sine wave multipliers according to the first aspect.

According to the present invention, the range of the level of the input signal can be widened with a simple configuration, and fluctuations in characteristics due to temperature can be reduced.

It is a figure which shows the structural example of the circuit which multiplies a square wave to an input signal. 1A shows a block diagram, and FIG. 1B shows an example of a circuit configuration. It is a figure which shows the frequency component of a sine wave and a square wave. FIG. 2A shows the frequency component of a square wave, and FIG. 2B shows the frequency component of a square wave. It is a figure which shows the frequency component of a square wave. 3A shows a frequency component of a square wave having a predetermined frequency, and FIGS. 3B and 3C show a frequency component of a square wave including a fundamental wave equal to the harmonic of the square wave of FIG. 3A. It is a figure which shows an example of a structure of the sine wave multiplication apparatus which concerns on 1st Embodiment. It is a figure which shows an example of a structure of the sine wave multiplication apparatus which concerns on 2nd Embodiment. It is a figure which shows an example of a structure of the square wave multiplication part in the sine wave multiplication apparatus which concerns on 2nd Embodiment. It is a timing diagram which shows the on-off state of each switch element of the square wave multiplication part in the sine wave multiplication apparatus which concerns on 2nd Embodiment, and a signal synthetic | combination part. It is a figure which shows an example of a structure of the square wave multiplication part in the sine wave multiplication apparatus which concerns on 3rd Embodiment. It is a timing diagram which shows the on-off state of each switch element of the square wave multiplication part in the sine wave multiplication apparatus which concerns on 3rd Embodiment, and a signal synthetic | combination part. It is a figure which shows an example of a structure of the sine wave multiplication apparatus which concerns on 4th Embodiment. It is a figure which shows the other structural example of the sine wave multiplication apparatus which concerns on 4th Embodiment. It is a figure which shows an example of a structure of the sine wave multiplication apparatus which concerns on 5th Embodiment. It is a figure which shows an example of a structure of the square wave multiplication part in the sine wave multiplication apparatus which concerns on 6th Embodiment. It is a timing diagram which shows the on-off state of each switch element of the square wave multiplication part in the sine wave multiplication apparatus which concerns on 6th Embodiment, and a signal synthetic | combination part. It is a figure which shows an example of a structure of the sine wave multiplication apparatus which concerns on 7th Embodiment. It is a figure which shows an example of a structure of the square wave multiplication part in the sine wave multiplication apparatus which concerns on 7th Embodiment. It is a timing diagram which shows the on-off state of each switch element of the square wave multiplication part in the sine wave multiplication apparatus which concerns on 7th Embodiment, and a signal synthetic | combination part. It is a figure which shows an example of a structure of the input device which concerns on 8th Embodiment. It is a figure which shows the modification of the sine wave multiplication apparatus which concerns on 1st Embodiment.

First, an outline of a method of multiplying an input signal by a sine wave in the sine wave multiplier according to the embodiment of the present invention will be described.

FIG. 1 is a diagram showing a configuration example of a circuit that multiplies an input signal Si by a square wave. Square wave multiplication is different from sine wave multiplication, and can be realized by a simple circuit using fixed gain amplifier circuits 2 and 4 and a switch circuit 3, for example, as shown in FIG. 1B. In the square wave multiplication circuit shown in FIG. 1B, an input signal Si or a signal obtained by inverting the input signal Si by the amplifier circuit 2 having a gain “−1” is input to the amplifier circuit 4 having a gain A through the switch circuit 3. In one half cycle of the square wave, the input signal Si is amplified (multiplied by A) by the amplifier circuit 4 having a gain A, and in the other half cycle of the square wave, the input signal Si has a gain A and a gain. Amplified by the amplifier circuit 2 of “−1” (multiplied by −A).

FIG. 2 is a diagram showing frequency components of a sine wave and a square wave. A sine wave consists of only a single frequency component as shown in FIG. 2A, while a square wave consists of a fundamental wave and a harmonic as shown in FIG. 2B. Accordingly, the square wave multiplication result signal shown in FIG. 1 includes a signal component obtained by multiplying the input signal Si by the fundamental wave (input signal Si × fundamental wave) and a signal component obtained by multiplying the input signal Si by the harmonic wave (input signal). (Si × harmonic).

As shown in FIG. 1, the multiplication of the square wave has an advantage that the circuit configuration is simple and it is difficult to be influenced by the temperature characteristics and input / output nonlinear characteristics of the transistor as in the case of using an analog multiplier. However, since the signal of the square wave multiplication result includes the harmonic signal component (input signal Si × harmonic) as described above, it cannot be used as it is as the multiplication result of the input signal Si and the sine wave. Therefore, in the sine wave multiplication device according to the present embodiment, a plurality of circuits that multiply the input signal and the square wave are provided, and their outputs are combined to be included in the multiplication result of the input signal and the square wave. Unnecessary signal components (input signal x harmonic) are canceled.

FIG. 3 is a diagram showing frequency components of a square wave. FIG. 3A shows the frequency component of a square wave of frequency fs. FIG. 3B shows frequency components of a square wave having a frequency (3fs) that is three times that of the square wave of FIG. 3A and an amplitude (A / 3) that is one third. FIG. 3C shows a frequency component of a square wave having a frequency (5 fs) five times that of the square wave of FIG. 3A and an amplitude (A / 5) of one fifth.

The square wave having the frequency fs includes a fundamental wave having the frequency fs and harmonics having frequencies (3fs, 5fs, 7fs,...) That are odd multiples thereof. When the amplitude of the fundamental wave is “B”, the amplitude of the harmonic having the frequency “K × fs” (hereinafter referred to as “Kth harmonic”) is “B / K”. The fundamental wave in the square wave of frequency 3fs and amplitude B / 3 shown in FIG. 3B is equal to the third harmonic in the square wave of frequency fs and amplitude B shown in FIG. 3A. Further, the fundamental wave in the square wave of frequency 5fs and amplitude B / 5 shown in FIG. 3C is equal to the fifth harmonic in the square wave of frequency fs and amplitude B shown in FIG. 3A.

Accordingly, by multiplying the input signal Si by the square wave shown in FIG. 3A, multiply the input signal Si by the square wave having the opposite phase to the square wave shown in FIGS. 3B and 3C, and synthesize the multiplication results. The third harmonic component and the fifth harmonic component in the square wave of frequency fs can be canceled out. As described above, in the sine wave multiplication device according to the present embodiment, instead of performing direct multiplication of the input signal and the sine wave using an analog multiplier, multiplication of the input signal and a plurality of square waves is performed. By multiplying the multiplication results, multiplication of the input signal and the sine wave is realized. For this reason, it is difficult to be influenced by the temperature characteristics and input / output nonlinear characteristics of the transistor, and the circuit configuration is simplified.

Next, some embodiments of the present invention will be described with reference to the drawings.

<First Embodiment>
FIG. 4 is a diagram illustrating an example of the configuration of the sine wave multiplier according to the first embodiment of the present invention. The sine wave multiplier shown in FIG. 1 includes three square wave multipliers U1, U2, and U3 that multiply square signals W1, W2, and W3 having different frequencies by an input signal Si, and the square wave multipliers U1, U2, and U3. A signal synthesizer 10 that synthesizes the output signals Su1, Su2, Su3 of U3 is provided. Hereinafter, an arbitrary one of the square wave multipliers U1 to U3 is referred to as a “square wave multiplier U”, an arbitrary one of the output signals Su1 to Su3 is referred to as an “output signal Su”, and the square waves W1 to W3 Arbitrary one is described as “square wave W”.

The square wave W multiplied by the input signal Si in the square wave multiplication unit U has a waveform with the same amplitude and opposite polarity in one half cycle and the other half cycle. This square wave W can be approximated as the sum of a fundamental wave and a harmonic wave as shown in FIGS. 2 and 3, and the Kth harmonic wave has a frequency K times that of the fundamental wave and an amplitude of 1 / K. have.

The square wave multiplier U generates, for example, an output signal Su proportional to the input signal Si in each of one half cycle and the other half cycle in one cycle of the square wave W to be multiplied by the input signal Si. The output signal Su is generated so that the absolute value of the ratio between the input signal Si and the output signal Su is equal in the half cycle and the other half cycle, and the sign of the ratio is inverted. That is, the square wave multiplication unit U sets the ratio of the output signal Su to the input signal Si in one half cycle in one cycle of the square wave W to “A”, and the other half cycle in one cycle of the square wave W. The ratio of the output signal Su to the input signal Si is “−A”.

The square wave multiplier U1 (hereinafter referred to as “first square wave multiplier U1”) has a square wave W1 having a sine wave of frequency fs as a fundamental wave (hereinafter referred to as “first square wave W1”). Is multiplied by the input signal Si. In the example of FIG. 4, the frequency of the first square wave W1 is “fs”, and the amplitude is “A”.

Square wave multipliers U2 and U3 (hereinafter referred to as “second square wave multiplier U2” and “second square wave multiplier U3”) are used to generate one harmonic wave included in first square wave W1 having frequency fs. Square waves W2 and W3 (hereinafter referred to as “second square wave W2” and “second square wave W3”) having sine waves with inverted phases as fundamental waves are respectively multiplied by the input signal Si.
That is, the second square wave multiplication unit U2 multiplies the input signal Si by a second square wave W2 having a sine wave obtained by inverting the phase of the third harmonic in the first square wave W1 as a fundamental wave. As shown in FIG. 4, the frequency of the second square wave W2 is “3fs” and the amplitude is “A / 3”.
The second square wave multiplication unit U3 multiplies the input signal Si by a second square wave W3 having a sine wave obtained by inverting the phase of the fifth harmonic in the first square wave W1 as a fundamental wave. As shown in FIG. 4, the frequency of the second square wave W3 is “5fs” and the amplitude is “A / 5”.

The signal synthesis unit 10 adds the output signal Su1 of the first square wave multiplication unit U1 and the output signals Su2 and Su3 of the second square wave multiplication units U2 and U3. The signal synthesizer 10 outputs the signal component corresponding to the product of the third harmonic of the first square wave W1 included in the output signal Su1 and the input signal Si by adding the output signals Su1 to Su3. The signal component is canceled by a signal component corresponding to the product of the fundamental wave of the second square wave W2 included in the signal Su2 and the input signal Si. Further, the signal synthesizer 10 generates a signal component corresponding to the product of the fifth harmonic of the first square wave W1 included in the output signal Su1 and the input signal Si, and the second square wave W3 included in the output signal Su3. Is canceled by a signal component corresponding to the product of the fundamental wave and the input signal Si.

Thus, according to the sine wave multiplier shown in FIG. 4, the signal component corresponding to the product of the third harmonic wave of the first square wave W1 included in the output signal Su1 and the input signal Si, and the first square A signal component corresponding to the product of the fifth harmonic of the wave W1 and the input signal Si, a signal component corresponding to the product of the fundamental wave of the second square wave W2 included in the output signal Su2 and the input signal Si, and The signal component corresponding to the product of the fundamental wave of the second square wave W3 included in the output signal Su3 and the input signal Si is canceled out. Therefore, in the output signal So obtained as a result of combining the output signals Su1 to Su3, signal components corresponding to the third harmonic and the fifth harmonic of the first square wave W1 are reduced, and the basic of the first square wave W1 is reduced. The signal component corresponding to the product of the wave (sine wave of frequency fs) and the input signal Si becomes the dominant component. Therefore, the output signal So corresponding to the product of the sine wave of the frequency fs and the input signal Si can be generated.

Further, according to the sine wave multiplication device shown in FIG. 4, in the square wave multiplication unit U, the input signal Si in one half cycle and the other half cycle in one cycle of the square wave W multiplied by the input signal Si. The output signal Su is generated so that the absolute value of the ratio between the output signal Su and the output signal Su is equal and the sign of the ratio is inverted. That is, the input signal Si and the square wave W are multiplied by inverting the positive / negative sign for each half cycle of the square wave W while maintaining the absolute value of the ratio (signal gain) of the output signal Su to the input signal Si. Done. Such multiplication of the square wave W is discrete signal processing in which a fixed signal gain is switched every half cycle, and the influence of the analog characteristics of the transistor current and voltage on the multiplication result is reduced. Therefore, it is possible to make it difficult to be influenced by the temperature characteristics and input / output nonlinear characteristics of the transistor as in the case of using an analog multiplier.

<Second Embodiment>
Next, an example of a more detailed configuration of the sine wave multiplier shown in FIG. 4 will be described as a second embodiment.

FIG. 5 is a diagram illustrating an example of the configuration of the sine wave multiplication device according to the second embodiment. FIG. 6 is a diagram showing an example of the configuration of square wave multipliers U1 to U3 (square wave multiplier U) in the sine wave multiplier shown in FIG.

The inputs of the square wave multipliers U1 to U3 are connected to an input node Ni to which an input signal Si is applied, and the outputs of the square wave multipliers U1 to U3 are connected to a common output node Nc.

The square wave multiplication unit U in the present embodiment outputs the multiplication result of the input signal Si and the square wave W as an electric charge. That is, the square wave multiplying unit U stores a charge proportional to the voltage of the input signal Si in each of one half cycle and the other half cycle in one cycle of the square wave W multiplied by the input signal Si. And a charge output operation for outputting the charge accumulated by the charging operation to the signal synthesizer 10 are alternately repeated at a predetermined sampling period T. Further, the square wave multiplication unit U calculates the voltage of the input signal Si and the amount of charge accumulated by the charging operation in one half cycle and the other half cycle in one cycle of the square wave W multiplied by the input signal Si. The charge operation and the charge output operation are performed so that the ratio (voltage / charge amount) is equal and the polarity of the charge output to the signal synthesis unit 10 is inverted.

For example, as illustrated in FIG. 6, the square wave multiplication unit U includes a first capacitor C1 and a second capacitor C2, a first switch unit 21 that performs a charge operation and a charge output operation of the first capacitor C1, and a second capacitor C2. And a second switch unit 22 for performing the charge operation and the charge output operation.

The first capacitor C1 is used for the charging operation and the charge output operation in one half cycle in one cycle of the square wave W multiplied by the input signal Si, and the second capacitor 2 is used in the other half cycle in the one cycle. Used for charge operation and charge output operation. The first capacitor C1 and the second capacitor C2 have the same capacitance.

The capacitances of the first capacitor C1 and the second capacitor C2 in the first square wave multiplier U1, the second square wave multiplier U2, and the third square wave multiplier U3 are the harmonics of the first square wave W1 and the second The fundamental waves of the square waves W2, W3 are set to have the same amplitude. The capacitances of the first capacitor C1 and the second capacitor C2 in the first square wave multiplication unit U1 are “Cu1”, and the capacitances of the first capacitor C1 and the second capacitor C2 in the second square wave multiplication unit U2 are “Cu2”. If the capacitances of the first capacitor C1 and the second capacitor C2 in the third square wave multiplication unit U3 are “Cu3”, these capacitances are set as follows.

The ratio between the electrostatic capacitance Cu1 and the electrostatic capacitance Cu2 is set as follows according to the ratio between the amplitude of the fundamental wave of the first square wave W1 and the amplitude of the third harmonic.

[Equation 1]
Cu1: Cu2 = 1: 1/3 (1)

By setting the ratio of the capacitances Cu1 and Cu2 as shown in Expression (1), the amount of charge output from the first square wave multiplier U1 by the third harmonic of the first square wave W1, and the second The amount of charge output from the second square wave multiplier U2 is equalized by the fundamental wave of the square wave W2. Since the third harmonic of the first square wave W1 and the fundamental wave of the second square wave W2 have opposite phases, the first square wave multiplier U1 according to the third harmonic of the first square wave W1. The charge output from the second square wave is canceled by the charge output from the second square wave multiplier U2 in accordance with the fundamental wave of the second square wave W2.

On the other hand, the ratio between the electrostatic capacitance Cu1 and the electrostatic capacitance Cu3 is set as follows according to the ratio between the amplitude of the fundamental wave of the first square wave W1 and the amplitude of the fifth harmonic.

[Equation 2]
Cu1: Cu3 = 1: 1/5 (2)

By setting the ratio of the capacitances Cu1 and Cu3 as shown in Expression (2), the amount of charge output from the first square wave multiplier U1 by the fifth harmonic of the first square wave W1 and the second It becomes equal to the amount of charge output from the second square wave multiplier U3 by the fundamental wave of the square wave W3. Since the fifth harmonic of the first square wave W1 and the fundamental wave of the second square wave W3 have opposite phases, the first square wave multiplier U1 according to the fifth harmonic of the first square wave W1. The charge output from the second wave is canceled by the charge output from the second square wave multiplier U3 in accordance with the fundamental wave of the second square wave W3.

From the formulas (1) and (2), the ratio of the capacitances Cu1, Cu2 and Cu3 is expressed by the following formula.

[Equation 3]
Cu1: Cu2: Cu3 = 1: 1/3: 1/5 = 15: 5: 3 (3)

The first switch unit 21 repeatedly performs the charging operation and the charge output operation of the first capacitor C1 in one half cycle of one cycle of the square wave W. In the half cycle in which the first switch unit 21 operates, the charging operation and the charge output operation of the second capacitor C2 by the second switch unit 22 are stopped.
When performing the charging operation of the first capacitor C1, the first switch unit 21 connects one end of the first capacitor C1 to the input node Ni and connects the other end of the first capacitor C1 to the reference potential. When performing the charge output operation of the first capacitor C2, the first switch unit 21 connects the one end of the first capacitor C1 to the output node Nc and connects the other end of the first capacitor C1 to the reference potential. The first switch unit 21 repeats the charging operation and the charge output operation alternately with the sampling period T.

The first switch unit 21 includes a first switch element SW1 and a second switch element SW2, for example, as shown in FIG. The first switch element SW1 is provided in a current path between the input node Ni and one end of the first capacitor C1. The second switch element SW2 is provided in a current path between the one end of the first capacitor C1 and the output node Nc. The other end of the first capacitor C1 is connected to a reference potential.

The second switch unit 22 repeatedly performs the charging operation and the charge output operation of the second capacitor C2 in the other half cycle in one cycle of the square wave W. In the other half cycle in which the second switch unit 22 operates, the charging operation and the charge output operation of the first capacitor C1 by the first switch unit 21 are stopped.
When performing the charging operation of the second capacitor C2, the second switch unit 22 connects one end of the second capacitor C2 to the input node Ni and connects the other end of the second capacitor C2 to the reference potential. When performing the charge output operation of the second capacitor C2, the second switch unit 22 connects the other end of the second capacitor C2 to the output node Nc and connects the one end of the second capacitor C2 to the reference potential. The second switch unit 22 repeats the charging operation and the charge output operation alternately with the sampling period T.

The second switch section 22 includes, for example, a third switch element SW3, a fourth switch element SW4, a fifth switch element SW5, and a sixth switch element SW6 as shown in FIG. The third switch element SW3 is provided in a current path between the input node Ni and one end of the second capacitor C2. The fourth switch element SW4 is provided in a current path between the other end of the second capacitor C2 and the reference potential. The fifth switch element SW5 is provided in a current path between the other end of the second capacitor C2 and the output node Nc. The sixth switch element SW6 is provided in a current path between one end of the second capacitor C2 and the reference potential.

The switch elements of the first switch unit 21 and the second switch unit 22 operate as follows.
In one half cycle of the square wave W in which the first switch unit 21 operates, the first switch element SW1 and the second switch element SW2 are alternately turned on. That is, when the charging operation of the first capacitor C1 is performed, the first switch element SW1 is turned on and the other switch elements are turned off. When the charge output operation of the second capacitor C2 is performed, the second switch element SW2 is turned on and the other switch elements are turned off.
In the other half cycle of the square wave W in which the second switch unit 22 operates, the pair of the third switch element SW3 and the fourth switch element SW4 and the pair of the fifth switch element SW5 and the sixth switch element SW6 are alternately turned on. To do. That is, when the charging operation of the second capacitor C2 is performed, the pair of the third switch element SW3 and the fourth switch element SW4 are both turned on and the other switch elements are turned off. When the charge output operation of the second capacitor C2 is performed, the pair of the fifth switch element SW5 and the sixth switch element SW6 are both turned on and the other switch elements are turned off.

In the charging operation and charge output operation of the first switch unit 21 and the charging operation and charge output operation of the second switch unit 22, the charge output to the signal synthesis unit 10 when the same input signal Si is given. The polarity is reversed. That is, when the input signal Si has a positive voltage with respect to the reference potential, a positive charge is output to the signal synthesis unit 10 by the charging operation and the charge output operation of the first switch unit 21, and the second switch unit 22 is charged. A negative charge is output to the signal synthesis unit 10 by the operation and the charge output operation. In the following description, an operation mode in which a positive charge is output to the signal synthesizer 10 when the input signal Si has a positive voltage with respect to the reference potential is referred to as a “forward rotation mode” and is negative to the signal synthesizer 10. The operation mode in which the electric charges are output is called “inversion mode”.

Each time the signal output unit 10 performs a predetermined number of charge output operations in the square wave multipliers (U1 to U3), the signal combiner 10 calculates the sum of the charges output from the square wave multipliers (U1 to U3). A corresponding output signal So is generated.

In the example of FIG. 5, the signal synthesis unit 10 includes a third capacitor C3, an amplifier circuit OP1, and a discharge circuit SWr.

The third capacitor C3 has one terminal connected to the output node Nc and the other terminal connected to the output of the amplifier circuit OP1.

The amplifier circuit OP1 controls the voltage of the other terminal of the third capacitor C3 so that the voltage difference between the output node Nc and the reference potential becomes zero. The amplifier circuit OP1 is an operational amplifier, for example, and an inverting input terminal is connected to the output node Nc, and a non-inverting input terminal is connected to a reference potential. In this case, the output node Nc connected to the inverting input terminal of the amplifier circuit OP1 is substantially equal to the reference potential.

The discharge circuit SWr discharges the charge accumulated in the third capacitor C3 each time a predetermined number of charge output operations are performed in the square wave multipliers (U1 to U3). For example, as shown in FIG. 5, the discharge circuit SWr is configured by a switch element connected in parallel with the third capacitor C3.

According to the configuration described above, when one terminal of the capacitor (C1, C2) is connected to the output node Nc by the charge output operation of the square wave multipliers (U1 to U3), at this time, the capacitor (C1, C2) Since the other terminal is connected to the reference potential and the output node Nc is kept at the reference potential by the amplifier circuit OP1, the charge accumulated in the capacitors (C1, C2) of the square wave multipliers (U1 to U3) is reduced. Transferred to the second capacitor C3. Therefore, the voltage of the output signal So of the amplifier circuit OP1 is a voltage corresponding to the sum of charges transferred from the capacitors (C1, C2) of the square wave multipliers (U1 to U3).

FIG. 7 is a timing chart showing the on / off states of the switch elements of the square wave multipliers (U1 to U3) and the signal synthesizer 10 in the sine wave multiplier according to the second embodiment. In the timing chart of FIG. 7, a high level indicates an on state of the switch element, and a low level indicates an off state of the switch element.

The first switch element SW1 and the second switch element SW2 that are alternately turned on are controlled so that the on states of the first switch element SW1 and the second switch element SW2 do not overlap each other in order to avoid crosstalk due to a delay in the on / off operation. The same applies to the pair of third switch element SW3 and fourth switch element SW4 that are alternately turned on and the pair of fifth switch element SW5 and sixth switch element SW6.

In the example of FIG. 7, one period (1 / fs) of the first square wave W1 is set to 60 cycles (60T) of the sampling period T, and one period (1/3 fs) of the second square wave W2 is the sampling period. T is set to 20 cycles (20T), and one cycle (1/5 fs) of the second square wave W3 is set to 12 cycles (12T) of the sampling cycle T.

The number of cycles of the sampling period T that defines the half period of the first square wave W1 (30 cycles in the example of FIG. 7) is the first square wave to be canceled by the output of the second square wave multiplier (U2, U3). The frequency of harmonics of W1 (3fs, 5fs) is set to be a common multiple of the magnification (3 times, 5 times) of the fundamental frequency fs. In the example of FIG. 5, since the third harmonic and the fifth harmonic of the first square wave W1 are harmonics to be canceled, “30” that is a common multiple of “3” and “5” is the first harmonic. It is set to the number of cycles of the sampling period T in the half period of one square wave W1. Thus, by determining the cycle number of the sampling period T in the half cycle of the first square wave W1, the cycle number of the sampling period T in the half cycle of the second square wave (W2, W3) can be set to an integer value. Therefore, the ratio between the period of the first square wave W1 and the period of the second square waves W2, W3 can be strictly set by the number of cycles of the sampling period T.

In the first square wave multiplication unit U1, the first switch unit 21 performs the forward mode operation 30 times in the first half cycle (30T) of the first square wave W1, and the second half cycle of the first square wave W1. At (30T), the second switch unit 22 performs the inversion mode operation 30 times.

In the second square wave multiplier U2, inversion mode operation is performed ten times by the second switch unit 22 in the first half cycle (10T) of the second square wave W2, and the second half cycle of the second square wave W2 ( 10T), the first switch unit 21 performs the forward rotation mode 10 times. When the first square wave multiplication unit U1 starts the forward rotation mode operation, the second square wave multiplication unit U2 starts the inversion mode operation. Therefore, the fundamental wave of the second square wave W2 is the first square wave W1. It has an opposite phase to the third harmonic.

In the second square wave multiplication unit U3, the second switch unit 22 performs the inversion mode operation six times in the first half cycle (6T) of the second square wave W3, and the second half wave of the second square wave W3 ( 6T), the first switch unit 21 performs the forward rotation mode six times. When the operation in the normal rotation mode is started in the first square wave multiplication unit U1, the operation in the inversion mode is started in the second square wave multiplication unit U3. Therefore, the fundamental wave of the second square wave W2 is the first square wave W1. Have the opposite phase to the fifth harmonic.

In the signal synthesis unit 10, the discharge circuit SWr is turned on every sampling cycle T in which the charging operation is performed in the square wave multiplication units U1 to U3, and the charge of the third capacitor C3 is discharged. A subsequent circuit (not shown) that processes the output signal So of the signal synthesizer 10 samples the output signal So while the discharge circuit SWr is off, and performs low-pass filter processing or analog processing on the sampled and held analog signal. Perform processing such as digital conversion.

In the example of FIG. 7, the charge of the third capacitor C3 is discharged every cycle of the sampling period T. However, if the amount of charge is very small, the discharge circuit SWr is turned on once every plural cycles of the sampling period T. It may be turned on. In this case, the subsequent circuit that processes the output signal So samples the output signal So immediately before the discharge circuit SWr is turned on. As a result, the amount of charge accumulated in the third capacitor C3 increases, so that the level of the output signal So can be increased.

As described above, according to the sine wave multiplication device according to the present embodiment, the charging operation and the charge output operation of the capacitors (C1, C2) are repeated at the sampling period T in the square wave multiplication unit U. By multiplying the polarity of the output charge in the charge output operation every half cycle, the input signal Si and the square wave W are multiplied. Therefore, the period and phase of the square wave in the square wave multiplication unit U can be strictly set by the number of cycles of the sampling period T. Further, since the capacitance ratio of the capacitors in the square wave multiplication unit U is not easily affected by variations due to temperature and manufacturing process, the ratio of the amplitudes of the square waves W multiplied by the input signal Si in each square wave multiplication unit U. Can be set with high accuracy. Therefore, the signal component (charge) corresponding to the product of the harmonic of the first square wave W1 included in the output of the first square wave multiplier U1 and the input signal Si is output to the outputs of the second square wave multipliers U2 and U3. Can be accurately canceled by the signal component (charge) corresponding to the product of the fundamental wave of the second square waves W2 and W3 and the input signal Si.

<Third Embodiment>
Next, a third embodiment of the present invention will be described.
The sine wave multiplier according to the third embodiment is obtained by replacing the square wave multipliers U1 to U3 in the sine wave multiplier according to the second embodiment with square wave multipliers UA1 to UA3 shown in FIG. In other respects, the configuration is the same as that of the sine wave multiplier according to the second embodiment.

The square wave multiplication units UA1 to UA3 include a first capacitor C1, a second capacitor C2, a fourth capacitor C4, a first switch unit 21A, and a second switch unit 22. Since the second switch unit 22 and the second capacitor C2 are the same as the components having the same reference numerals in FIG. 6, the description thereof is omitted here.

The first switch unit 21A includes switch elements (SW1, SW2) similar to those of the first switch unit 21, and includes a seventh switch element SW7, an eighth switch element SW8, and a ninth switch element SW9.
The fourth capacitor C4 is provided in the current path between the first switch element SW1 and the input node Ni. The seventh switch element SW7 is provided in a current path between one end of the fourth capacitor C4 and the input node Ni. The eighth switch element SW8 is provided in a current path between the one end of the fourth capacitor C4 and a reference potential. The ninth switch element SW9 is provided between the other end of the fourth capacitor C4 and the reference potential.

FIG. 9 is a timing chart showing the on / off states of the switch elements of the square wave multipliers (UA1 to UA3) and the signal synthesizer 10 in the sine wave multiplier according to the third embodiment.
As shown in FIG. 9, the seventh switch element SW7 is turned on / off under the same conditions as the first switch element SW1. The eighth switch element SW8 and the ninth switch element SW9 are turned on / off under the same conditions as the second switch element SW2. The operation of the other switch elements is the same as the timing chart shown in FIG.

The two switch elements (SW1, SW2) connected to the terminal that is not connected to the reference potential in the first capacitor C1 give unnecessary charges to the first capacitor C1 due to charging / discharging of the parasitic capacitance. Unnecessary charges may cause errors, which may reduce the accuracy of multiplication processing. Therefore, in the square wave multipliers UA1 to UA3 shown in FIG. 8, the series circuit of the first capacitor C1 and the fourth capacitor C4 is charged by the input signal Si during the charging operation, and the charge of the first capacitor C1 is charged during the charge output operation. The signal is output to the signal synthesizer 10 and both ends of the fourth capacitor C4 are connected to the reference potential to discharge the charge. By such an operation, unnecessary charges given to the first capacitor C1 due to charging / discharging of the parasitic capacitances of the switch elements (SW1, SW2, SW9) can be canceled.

In the square wave multipliers UA1 to UA3 shown in FIG. 8, since the charge is charged by the series circuit of the first capacitor C1 and the fourth capacitor C4 during the charging operation, the series circuit of the first capacitor C1 and the fourth capacitor C4. The capacitances of the first capacitor C1 and the fourth capacitor C4 are set so that the capacitance of the first capacitor C1 and the capacitance of the second capacitor C2 are equal. For example, the capacitances of the first capacitor C1 and the fourth capacitor C4 are set to twice the capacitance of the second capacitor C2.

<Fourth Embodiment>
Next, a fourth embodiment of the present invention will be described.
FIG. 10 is a diagram illustrating an example of the configuration of the sine wave multiplication device according to the fourth embodiment. The sine wave multiplier shown in FIG. 10 is obtained by providing the first low-pass filter 30 in the sine wave multiplier (FIG. 5) according to the second and third embodiments, and the other configurations are the second and third. This is the same as the sine wave multiplier according to the embodiment.

In the sine wave multipliers according to the second and third embodiments, since the input signal Si is discretely processed in the square wave multipliers (U1 to U3, UA1 to U3), the output of the square wave multiplier is There is a possibility that aliasing noise will occur. The first low-pass filter 30 is for reducing the aliasing noise, and attenuates the high-frequency component of the input signal Si input to the square wave multiplication unit. That is, the first low-pass filter 30 is a noise component included in the input signal Si, and a noise component that can cause aliasing from a frequency that is an integral multiple of the sampling frequency (1 / T) to the signal band of the input signal Si. Attenuate. Thereby, even when the input signal Si includes noise having a relatively high frequency, it is possible to prevent aliasing noise to the signal band of the input signal Si and perform highly accurate multiplication processing.

Further, by combining the outputs of the square wave multipliers (U1 to U3, UA1 to U3), components (harmonics × input signals) caused by the third and fifth harmonics of the first square wave W1. Si) can be canceled out, but the first square wave W1 has other harmonics that are not canceled out. Therefore, components due to these harmonics remain in the output signal So. In particular, the seventh harmonic having the next largest amplitude after the fifth harmonic may affect the accuracy of the multiplication result.

Further, as shown in FIG. 3, the second square waves W2 and W3 (FIGS. 3B and 3C) are not only the fundamental wave, but also their harmonics are some harmonics of the first square wave W1 (FIG. 3A). Is equal to In the example of FIG. 3, the third and fifth harmonics of the second square wave W2 are equal to the ninth and fifteenth harmonics of the first square wave W1. Further, the third harmonic of the second square wave W3 is equal to the fifteenth harmonic of the first square wave W1. Therefore, since the 15th harmonic of the first square wave W1 is subtracted by both the second square wave W2 and the second square wave W3, an error occurs.

Therefore, the first low-pass filter 30 attenuates the high-frequency component of the input signal Si before inputting it to the square wave multipliers (U1 to U3, UA1 to U3). Since the lowest harmonic that may affect the accuracy is the seventh harmonic (frequency 7 fs) of the first square wave W1, the frequency characteristic of the first low-pass filter 30 is a component having a frequency higher than the frequency 7 fs. Is set to attenuate to the extent that does not affect the multiplication accuracy.

FIG. 11 is a diagram illustrating another configuration example of the sine wave multiplication device according to the fourth embodiment. The sine wave multiplier shown in FIG. 11 is obtained by adding a second low-pass filter 40 to the sine wave multiplier shown in FIG. 10, and the other configuration is the same as the sine wave multiplier shown in FIG.

The sine wave multiplier shown in FIG. 11 can be operated as a circuit (narrowband bandpass filter circuit) that extracts only the signal component of the frequency fs contained in the input signal Si. In this case, by extracting the DC component of the output signal So by the second low-pass filter 40, the level of the DC component becomes a level corresponding to the amplitude of the signal component of the frequency fs included in the input signal Si. The second low-pass filter 40 is configured by, for example, a digital filter that discretely processes the AD conversion result of the output signal So.

<Fifth Embodiment>
Next, a fifth embodiment of the present invention will be described.
FIG. 12 is a diagram illustrating an example of the configuration of the sine wave multiplier according to the fifth embodiment. The sine wave multiplier shown in FIG. 12 has a low-pass filter 50 provided in the sine wave multiplier (FIG. 5) according to the second and third embodiments, and the input signal Si is a DC voltage VDD. The configuration is the same as that of the sine wave multiplier according to the second and third embodiments.

In the sine wave multiplier shown in FIG. 12, since the input signal Si is the DC voltage VDD, the output signal So is a signal obtained by multiplying the DC voltage VDD and the sine wave, that is, a sine wave. The sine wave multiplier shown in FIG. 10 converts the signal component of frequency fs into a direct current component. However, since the sine wave multiplier shown in FIG. 12 generates a signal of frequency fs from the direct current component, the input / output relationship. Is reversed. Therefore, the low-pass filter 50 attenuates a component having a frequency higher than the seventh harmonic component (frequency fs), similarly to the sine wave multiplier shown in FIG.
Thus, the sine wave multiplication device according to the present embodiment can be operated as a highly accurate sine wave generation circuit.

<Sixth Embodiment>
Next, a sixth embodiment of the present invention will be described.
FIG. 13 is a diagram illustrating an example of the configuration of the square wave multipliers UB1 to UB3 in the sine wave multiplier according to the sixth embodiment. The sine wave multiplier according to the third embodiment is obtained by replacing the square wave multipliers U1 to U3 in the sine wave multiplier according to the second embodiment with square wave multipliers UB1 to UB3 shown in FIG. In other respects, the configuration is the same as that of the sine wave multiplier according to the second embodiment.

6 and 8, the two capacitors (C1, C2) are provided independently for the normal rotation mode and the inversion mode, but in the square wave multiplication units UB1 to UB3 shown in FIG. The common capacitor C2 is used in the normal rotation mode and the inversion mode.

The square wave multipliers UB1 to UB3 include a third switch unit 23 and a second capacitor C2 in the example of FIG. The third switch unit 23 includes a tenth switch element SW10 in addition to the same switch elements (SW3, SW4, SW5, SW6) as the second switch unit 22. The connection relationship between the second capacitor C2 and the switch elements (SW3, SW4, SW5, SW6) is the same as in FIGS. The tenth switch element SW10 is provided in the current path between one end of the second capacitor C2 to which the third switch element SW3 and the sixth switch element SW6 are connected and the output node Nc.

FIG. 14 is a timing chart showing the on / off states of the switch elements of the square wave multipliers UB1 to UB3 and the signal synthesizer 10 in the sine wave multiplier according to the sixth embodiment.
In the forward rotation mode, the fourth switch element SW4 is always on. In the charging operation in the forward rotation mode, the third switch element SW3 is turned on, and the other switch elements except for the fourth switch element SW4 are turned off. In the charge output operation in the forward rotation mode, the tenth switch element SW10 is turned on, and the other switch elements other than the fourth switch element SW4 are turned off.
On the other hand, in the inversion mode, the tenth switch element SW10 is always in the off state. In the charging operation in the inversion mode, the pair of the third switch element SW3 and the fourth switch element SW4 is turned on, and the other switch elements are turned off. In the charge output operation in the inversion mode, the fifth switch element SW5 and the sixth switch element SW6 are turned on, and the other switch elements are turned off. This operation is the same as that of the second switch unit 22 in FIGS.

Thus, according to the present embodiment, since one capacitor C2 is used in both the normal rotation mode and the inversion mode, the circuit configuration can be simplified.

<Seventh Embodiment>
Next, a seventh embodiment of the present invention will be described.
FIG. 15 is a diagram illustrating an example of the configuration of the sine wave multiplication device according to the seventh embodiment. The sine wave multiplication device shown in FIG. 15 has an inverting amplifier circuit 60, square wave multiplication units UD1 to UD3, and a signal synthesis unit 10A.

The inverting amplifier circuit 60 is a circuit that inverts the polarity of the input signal Si with respect to the reference potential, and inputs the result obtained by multiplying the input signal Si by the gain “−1” to the square wave multipliers UD1 to UD3 as the inverted input signal -Si. To do.

The square wave multipliers UD1 to UD3 receive the input signal Si and the inverted input signal −Si, respectively, and in one half cycle of the square waves W1 to W3 that multiply the input signal Si, The output signals Sud1 to Sud3 proportional to the ratio are generated, and the output signals Sud1 to Sud3 proportional to the inverting input signal -Si at the predetermined ratio are generated in the other half cycle of the one cycle.
Hereinafter, in the present embodiment, any one of the square wave multipliers UD1 to UD3 is referred to as “square wave multiplier UD”, and any one of the output signals Sud1 to Sud3 is referred to as “output signal Sud”. An arbitrary one of the waves W1 to W3 is referred to as a “square wave W”.

FIG. 16 is a diagram illustrating an example of the configuration of the square wave multiplication unit UD. A square wave multiplier UD shown in FIG. 16 includes a resistor R1, a switch element SW12, and a switch element SW13.
The switch element SW13 is provided in a current path between one end of the resistor R1 and the input node NiX connected to the output of the inverting amplifier circuit 60. The switch element SW12 is provided in a current path between the one end of the resistor R1 and the input node Ni. The other end of the resistor R1 is connected to the output node Nc. In one half cycle of the square wave W, the switch element SW12 is turned on and the switch element SW13 is turned off. In the other half cycle, the switch element SW12 is turned off and the switch element SW13 is turned on.
Hereinafter, in the present embodiment, the operation mode during the half cycle of the square wave W in which the switch element SW12 is turned on and the switch element SW13 is turned off is referred to as a “forward rotation mode”. The operation mode during the other half cycle of the wave W is called “inversion mode”.

In the normal rotation mode, the input node Ni is connected to the output node Nc via the resistor R1. Since the output node Nc is maintained at a reference potential by a signal synthesis unit 10A described later, the current output from the square wave multiplication unit UD to the signal synthesis unit 10A has a value proportional to the voltage of the input signal Si. The ratio of the output current to the voltage of the input signal Si is the conductivity of the resistor R1.

On the other hand, in the inversion mode, the input node NiX is connected to the output node Nc via the resistor R1. Also in this case, since the output node Nc is kept at the reference potential, the current output from the square wave multiplier UD to the signal synthesizer 10A has a value proportional to the voltage of the inverted input signal -Si. The ratio of the output current to the voltage of the inverting input signal -Si is the conductivity of the resistor R1.

Square wave multiplier UD1 (hereinafter referred to as “first square wave multiplier UD1”) is a square wave W1 having a sine wave of frequency fs as a fundamental wave (hereinafter referred to as “first square wave W1”). Is multiplied by the input signal Si. The frequency of the first square wave W1 is “fs”, and the amplitude is “A”.
The square wave multipliers UD2 and UD3 (hereinafter referred to as “second square wave multiplier U2” and “second square wave multiplier UD3”) include third harmonics included in the first square wave W1 having the frequency fs. , Square waves W2 and W3 (hereinafter referred to as “second square wave W2” and “second square wave W3”) having sine waves obtained by inverting the phase of the fifth harmonic as fundamental waves, respectively. Multiply by. The frequency of the second square wave W2 is “3fs” and the amplitude is “A / 3”, the frequency of the second square wave W3 is “5fs”, and the amplitude is “A / 5”.

The conductivity of the resistor R1 in the first square wave multiplier UD1 is “Yu1”, the conductivity of the resistor R1 in the second square wave multiplier UD2 is “Yu2”, and the conductivity of the resistor R1 in the third square wave multiplier UD3 is Assuming “Yu3”, these electrical conductivities are set to a ratio represented by the following equation.

[Equation 4]
Yu1: Yu2: Yu3 = 15: 5: 3 (4)

By setting the conductivity as shown in Equation (4), the amplitude of the current component corresponding to the third harmonic of the first square wave W1 included in the output current of the first square wave multiplier UD1, The amplitude of the current component corresponding to the fundamental wave of the second square wave W2 included in the output current of the two square wave multiplier UD2 becomes equal. Further, the amplitude of the current component corresponding to the fifth harmonic of the first square wave W1 included in the output current of the first square wave multiplier UD1, and the second included in the output current of the second square wave multiplier UD3. The amplitude of the current component corresponding to the fundamental wave of the square wave W3 becomes equal.

The signal synthesis unit 10A generates an output signal So corresponding to the sum of the currents output from the square wave multiplication units UD1 to UD3. For example, as shown in FIG. 15, the signal synthesis unit 10A includes a resistor R3 and an amplifier circuit OP2. The resistor R3 is connected between the output node Nc and the output of the amplifier circuit OP2. The amplifier circuit OP2 controls the output voltage at one end of the resistor R3 so that the output node Nc becomes equal to the reference potential. The amplifier circuit OP2 is an operational amplifier, for example, and has an inverting input terminal connected to the output node Nc and a non-inverting input terminal connected to a reference potential.

FIG. 17 is a timing chart showing the on / off states of the switch elements of the square wave multipliers UD1 to UD3.
As shown in FIG. 17, while the first square wave multiplication unit UD1 performs one cycle multiplication of the first square wave W1 composed of the normal mode and the inversion mode, the second square wave multiplication unit UD2 performs the second square shape. The wave W2 is multiplied by 3 cycles, and the second square wave multiplier UD3 multiplies the second square wave W3 by 5 cycles.

Further, when the first square wave multiplication unit UD1 starts the forward rotation mode of the first square wave W1, the second square wave multiplication unit UD2 starts the inversion mode of the second square wave W2, and the second square wave multiplication. In the part UD3, the inversion mode of the second square wave W3 is started. Therefore, the fundamental wave of the second square wave W2 has an opposite phase to the third harmonic of the first square wave W1, and the fundamental wave of the second square wave W3 becomes the fifth harmonic of the first square wave W1. On the other hand, it becomes an antiphase. Therefore, the current component corresponding to the third harmonic of the first square wave W1 included in the output current of the first square wave multiplier UD1 is the second square wave included in the output current of the second square wave multiplier UD2. It is canceled by the current component corresponding to the fundamental wave of W2. The current component corresponding to the fifth harmonic of the first square wave W1 included in the output current of the first square wave multiplier UD1 is the second square wave included in the output current of the second square wave multiplier UD3. It is canceled out by the current component corresponding to the fundamental wave of W3.

As described above, also in the sine wave multiplication device according to the present embodiment, the input signal Si and the sine wave can be accurately multiplied with a simple configuration as in the embodiments described above.

<Eighth Embodiment>
Next, an input device according to an eighth embodiment of the invention will be described with reference to FIG.

The input device according to the present embodiment illustrated in FIG. 18 is an input device such as a touch sensor that inputs information according to the proximity of an object, and includes a sensor unit 110, a selection unit 120, a detection signal generation unit 130, 1 sine wave multiplication unit 140, second sine wave multiplication unit 150, and low-pass filter 160 are provided.

The sensor unit 110 includes a sensor element whose capacitance changes in accordance with the proximity of an object. In the example of FIG. 18, the sensor unit 110 includes electrodes ES1 to ESn that form capacitors with the object. When an object (such as a fingertip) approaches the electrodes ES1 to ESn, the capacitance of the capacitor formed between the electrodes ES1 to ESn and the object changes.

The selection unit 120 selects one of the electrodes ES1 to ESn in the sensor unit 110 and connects it to the input of the detection signal generation unit 130.

The detection signal generation unit 130 applies a sine wave drive voltage corresponding to the first sine wave supplied by the first sine wave multiplication unit 140 to the electrodes (ES1 to ESn) of the sensor unit 110 selected by the selection unit 120. And a detection signal Sn corresponding to the current flowing in the electrode is generated by applying the drive voltage. The detection signal generation unit 130 includes an operational amplifier OP3, a capacitor Cf, and a subtracter 131, for example, as shown in FIG. The capacitor Cf is connected between the inverting input terminal and the output terminal of the operational amplifier OP3. The first sine wave of the first sine wave multiplier 140 is input to the non-inverting input terminal of the operational amplifier OP3. The subtracter 131 subtracts the first sine wave from the output signal of the operational amplifier OP3 and outputs the subtraction result as the detection signal Sn. The detection signal Sn is a signal that vibrates at the same frequency fs as the first sine wave, and the amplitude thereof is proportional to the capacitance formed between the electrode of the sensor unit 110 and the object (fingertip).

The first sine wave multiplication unit 140 is a circuit that multiplies a DC signal by a sine wave having a frequency fs and outputs a first sine wave having a predetermined frequency as a result of the multiplication. For example, the first sine wave multiplication device shown in FIG. It has the same configuration as.

The second sine wave multiplication unit 150 is a circuit that multiplies the detection signal Sn generated by the detection signal generation unit 130 by the second sine wave having the frequency fs. For example, the second sine wave multiplication unit 150 has the same configuration as the sine wave multiplication device shown in FIG. Have

The low-pass filter 160 extracts a DC component signal Da from the signal Ds obtained as a multiplication result of the second sine wave multiplication unit 150. The second sine wave multiplier 150 and the low-pass filter 160 operate as a narrow-band band-pass filter that extracts a signal component of the frequency fs included in the detection signal Sn. The DC component signal Da has a level corresponding to the amplitude of the signal component of the frequency fs included in the detection signal Sn, and is an electrostatic capacitance formed between the electrode of the sensor unit 110 and the object (fingertip). Is proportional to

According to the input device according to the present embodiment, the first sine wave multiplication unit 140 and the second sine wave multiplication unit 150 having a simple configuration are used to detect capacitance with high accuracy from which the influence of external noise has been removed. A value can be obtained.

As mentioned above, although several embodiment of this invention was described, this invention is not limited only to these embodiment, Furthermore, various variations are included.

In the sine wave multiplier shown in FIG. 4, the phase of the fundamental wave of the second square wave W2, W3 multiplied by the input signal Si in the second square wave multiplier U2, U3 is changed to the phase of the harmonic wave in the first square wave W1. In contrast, the present invention is not limited to this example. In another embodiment of the present invention, for example, as shown in FIG. 19, the phase of the fundamental wave of the second square waves W2, W3 multiplied by the input signal Si in the second square wave multipliers U2, U3 is changed to the first square wave. You may make it become the same phase as the phase of the harmonic in W1. In this case, the signal combining unit 10 combines the signals so as to subtract the output signals Su2 and Su3 of the second square wave multipliers U2 and U3 from the output signal Su1 of the first square wave multiplier U1. The harmonic component can be canceled as in the sine wave multiplier shown in FIG.

In the embodiment described above, the signal components corresponding to the third harmonic and the fifth harmonic in the first square wave W1 are canceled by the signal components corresponding to the fundamental waves of the second square waves W2 and W3. The present invention is not limited to this example. In another embodiment of the present invention, the number of square wave multipliers may be three or more so that signal components corresponding to higher harmonics can be canceled.

In the above-described embodiment, an example in which signal processing is performed based on the signal level from the reference potential has been described. However, in another embodiment of the present invention, a configuration in which a differential signal is handled may be employed. Thereby, it can be made hard to receive the influence of disturbances, such as power supply noise.

In the embodiment described above, square wave multiplication processing and multiplication result synthesis processing are performed by analog circuits. However, in other embodiments of the present invention, these signal processing may be performed by digital signal processing.

DESCRIPTION OF SYMBOLS 10,10A ... Signal synthetic | combination part, 21, 21A ... 1st switch part, 22 ... 2nd switch part, 23 ... 3rd switch part, 30 ... 1st low pass filter, 40 ... 2nd low pass filter, 50, 160 ... low pass Filter, 60 ... Inverting amplifier, U1 to U3, UA1 to UA3, UB1 to UB3, UD1 to UD3 ... Square wave multiplier, SW1 to SW10 ... Switch element, OP1, OP2 ... Amplifier circuit, C1-C4 ... Capacitor, R1 ... resistance

Claims (12)

1. A sine wave multiplier for multiplying an input signal by a sine wave of a predetermined frequency,
   A plurality of square wave multipliers for multiplying the input signal by square waves of different frequencies,
   A signal synthesis unit that synthesizes output signals of the plurality of square wave multiplication units,
   The square wave can be approximated as the sum of a fundamental wave that is the lowest sine wave and a plurality of harmonics that are sine waves each having an integer multiple of the fundamental wave,
   The plurality of square wave multiplication units include one first square wave multiplication unit and one or more second square wave multiplication units,
   The first square wave multiplication unit multiplies the input signal by a first square wave having the sine wave of the predetermined frequency as the fundamental wave,
   The second square wave multiplication unit is a second square wave having the fundamental wave as a sine wave equal to one harmonic included in the first square wave or a sine wave obtained by inverting the phase of the one harmonic. Multiplied by the input signal,
   The signal synthesis unit converts a signal component corresponding to a product of at least one harmonic of the first square wave included in the output signal of the first square wave multiplication unit and the input signal into the second square wave. A sine wave multiplication device characterized by canceling with a signal component corresponding to a product of the fundamental wave of the second square wave and the input signal included in an output signal of a multiplication unit.
2. The square wave multiplication unit generates an output signal proportional to the input signal in each of one half cycle and the other half cycle in one cycle of the square wave multiplied by the input signal, and The output signal is generated so that the absolute value of the ratio between the input signal and the output signal is equal in the period and the other half period, and the sign of the ratio is inverted. The sine wave multiplication device according to 1.
3. The square wave multiplying unit stores a charge proportional to the voltage of the input signal in each of one half cycle and the other half cycle in one cycle of the square wave multiplied by the input signal; The charge output operation of outputting the charge accumulated by the charging operation to the signal synthesizer is alternately repeated at a predetermined sampling period, and the input signal in the half cycle and the other half cycle is repeated. The charge operation and the charge output operation are performed so that the ratio of the voltage and the amount of charge accumulated by the charge operation is equal, and the polarity of the charge output to the signal synthesis unit is inverted,
   The signal synthesis unit responds to the sum of the charges output from the plurality of square wave multiplication units by the charge output operation each time the charge output operation is performed a predetermined number of times in the plurality of square wave multiplication units. The sine wave multiplication device according to claim 2, wherein a signal is generated.
4. The first square wave multiplication unit and the second square wave multiplication unit have at least one capacitor that accumulates electric charge in the charging operation,
   A ratio of the capacitance of the capacitor in which the first square wave multiplication unit accumulates electric charge in the charging operation to the capacitance of the capacitor in which the second square wave multiplication unit accumulates electric charge in the charging operation is A value corresponding to a ratio between the amplitude of the fundamental wave of the first square wave and the amplitude of the harmonic wave of the first square wave having the same frequency as the fundamental wave of the second square wave. The sine wave multiplication device according to claim 3, wherein
5. An input node to which the input signal is input;
   An output node to which outputs of the plurality of square wave multipliers are connected in common,
   The square wave multiplier is
   A first capacitor and a second capacitor;
   A charging operation of connecting one end of the first capacitor to the input node and connecting the other end of the first capacitor to a reference potential in one half cycle of the square wave multiplied by the input signal; And a first switch unit that alternately repeats the charge output operation of connecting the one end of the first capacitor to the output node and connecting the other end of the first capacitor to the reference potential in the sampling period;
   Charging operation for connecting one end of the second capacitor to the input node and connecting the other end of the second capacitor to the reference potential in the other half cycle of the square wave multiplied by the input signal And a second switch unit that alternately repeats the charge output operation of connecting the other end of the second capacitor to the output node and connecting the one end of the second capacitor to the reference potential in the sampling period. Have
   The signal synthesizer
   A third capacitor having one terminal connected to the output node;
   An amplifier circuit for controlling the voltage of the other terminal of the third capacitor so that the voltage difference between the output node and the reference potential becomes zero;
   5. The discharge circuit according to claim 3, further comprising: a discharge circuit that discharges the charge accumulated in the third capacitor each time the charge output operation is performed a predetermined number of times in the plurality of square wave multiplication units. Sine wave multiplier.
6. The first switch unit includes:
   A first switch element provided in a current path between the input node and the one end of the first capacitor;
   A second switch element provided in a current path between the one end of the first capacitor and the output node;
   The other end of the first capacitor is connected to the reference potential;
   The second switch unit is
   A third switch element provided in a current path between the input node and the one end of the second capacitor;
   A fourth switch element provided in a current path between the other end of the second capacitor and the reference potential;
   A fifth switch element provided in a current path between the other end of the second capacitor and the output node;
   A sixth switch element provided in a current path between the one end of the second capacitor and the reference potential;
   In one half cycle of one cycle of the square wave multiplied by the input signal,
   During the charging operation, the first switch element is turned on and the other switch elements are turned off,
   In the charge output operation, the second switch element is turned on and the other switch elements are turned off.
   In the other half cycle in one cycle of the square wave multiplied by the input signal,
   The third switch element and the fourth switch element are turned on and the other switch elements are turned off during the charging operation,
   6. The sine wave multiplication device according to claim 5, wherein, during the charge output operation, the fifth switch element and the sixth switch element are turned on and the other switch elements are turned off.
7. The square wave multiplier has a fourth capacitor provided in a current path between the first switch element and the input node,
   The first switch unit includes:
   A seventh switch element provided in a current path between one end of the fourth capacitor and the input node;
   An eighth switch element provided in a current path between the one end of the fourth capacitor and the reference potential;
   A ninth switch element provided in a current path between the other end of the fourth capacitor and the reference potential;
   The seventh switch element is turned on and off under the same conditions as the first switch element;
   The sine wave multiplication device according to claim 6, wherein the eighth switch element and the ninth switch element are turned on and off under the same conditions as the second switch element.
8. Attenuating the noise component included in the input signal input to the plurality of square wave multipliers, which may cause aliasing from a frequency that is an integral multiple of the sampling frequency to the signal band of the input signal. The sine wave multiplication device according to any one of claims 3 to 7, further comprising a first low-pass filter.
9. The square wave multiplication unit inputs the input signal and an inverted input signal in which the polarity of the input signal is inverted, respectively, and in one half cycle of one cycle of the square wave multiplied by the input signal, the input signal is predetermined. 3. The sine according to claim 2, wherein an output signal proportional to the ratio is generated, and an output signal proportional to the inverted input signal is generated in the other half cycle in the one period. Wave multiplier.
10. The square wave multiplication unit generates an output current proportional to the voltage of the input signal at a predetermined ratio in one half cycle of a square wave multiplied by the input signal, and the other half in the one cycle. Generating an output current proportional to the voltage of the inverting input signal at the predetermined ratio in a period;
    The sine wave multiplication device according to claim 9, wherein the signal synthesis unit generates a signal corresponding to a sum of the output currents output from the plurality of square wave multiplication units.
11. N of the harmonics included in the first square wave are multiplied by the input signal by N patterns of the second square waves corresponding to the first to Nth harmonics in order of decreasing frequency. The square wave multiplier of
    A second that attenuates the harmonics included in the first square wave, the (N + 1) -th and higher harmonics in order of decreasing frequency, from a signal output as a result of synthesis in the signal synthesis unit; It has a low-pass filter. The sine wave multiplication apparatus as described in any one of Claims 1 thru | or 10 characterized by the above-mentioned.
12. An input device for inputting information according to the proximity of an object,
    A sensor unit including a sensor element whose capacitance changes according to the proximity of the object;
    A first sine wave multiplier that multiplies a DC signal by a sine wave of a predetermined frequency and outputs the first sine wave of the predetermined frequency as a result of the multiplication;
    A detection signal generation unit configured to apply a drive voltage of a sine wave corresponding to the first sine wave to the sensor element, and to generate a detection signal corresponding to a current flowing through the sensor element by the application of the drive voltage;
    A second sine wave multiplier for multiplying the detection signal by a second sine wave of the predetermined frequency;
    A low-pass filter that extracts a direct current component from the signal of the multiplication result of the second sine wave multiplier,
    The input device according to claim 1, wherein the first sine wave multiplication unit and the second sine wave multiplication unit are the sine wave multiplication device according to claim 1.

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